ON NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 handbook
Contents
1. 1 02 8 6 E STARTUP 1 00 x 84 THRESHOLD 2 VCcC on E a z 0 98 c 8 2 a E T 0 96 n 80 2 ke MINIMUM Q 0 94 E 7 8 OPERATING N THRESHOLD 2 a 7 6 VcC off o camem Sri 2 0 90 74 0 88 7 2 50 25 0 25 50 75 100 125 150 50 25 0 25 50 75 100 125 150 TEMPERATURE C TEMPERATURE C Figure 17 Normalized Peak Current Limit Figure 18 Supply Voltage Thresholds versus versus Temperature Temperature 4 56 gt 4 54 d 4 52 P I 4 50 E t E tr 4 48 5 E 4 46 E 5 444 5 lt O c 4 42 gt 4 40 E m ep W 4 38 S 4 36 4 34 50 25 0 25 50 75 100 125 150 50 25 0 25 50 75 100 125 150 TEMPERATURE C TEMPERATURE C Figure 19 Undervoltage Lockout Threshold Figure 20 Start Current versus Temperature versus Temperature T T E E E E Z Z LU LU a a a a DI O a a D E E a a E E v o 0 1 2 3 4 5 6 7 8 9 1 10 100 1000 SUPPLY VOLTAGE V PIN 5 VOLTAGE V Figure 21 Startup Current versus Supply Figure 22 Startup Current versus Pin 5 Voltage Voltage http onsemi com 12 SUPPLY CURRENT mA SUPPLY CURRENT mA NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP10552. 50 1 39 1 38 de CURRENT RISING 1 37 gt 1 36 LU 1 42 g 1 35 F 1 34 9 133 Isink 25 pA 38 a CURRENT FALLING 2 1 32 a 131 1 30 1 29 1 28 50 25 0 25 50 75 100 125 150 50 25 0 25 50 75 100 125 150 TEMPERATURE C TEMPERATURE C Figure 11 Upper Window Control Input Figure 12 Control Input Lower Window Clamp Current Thresholds versus Temperature Voltage versus Temperature 4 66 45 4 4 64 0 35 4 62 a w 30 2 4 60 lt 25 a 4 58 ISOURCE 25 uA c 20 e fe NCP1053 4 5 4 56 z Ip 100 mA O 4 54 4 52 50 25 0 25 50 75 100 125 150 50 25 0 25 50 75 100 125 150 TEMPERATURE C TEMPERATURE C Figure 13 Control Input Upper Window Clamp Figure 14 On Resistance versus Temperature Voltage versus Temperature 120 100 Ty 25 C J 100 a NCP1053 4 5 80 2 LU 2 60 10 Ty 40 C Q NCP1050 1 2 4 40 E Ty 25 C o 20 Ty 125 C 0 1 0 100 200 300 400 500 600 700 800 900 0 100 200 300 400 500 600 700 APPLIED VOLTAGE V Figure 15 Power Switch and Startup Circuit Leakage Current versus Voltage APPLIED VOLTAGE V Figure 16 Power Switch and Startup Circuit Output Capacitance versus Applied Voltage http onsemi com 11 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055
3. 0 55 0 70 0 65 T oe E 0 60 Er Z te 0 55 0 45 5 O 0 50 a 0 40 m 0 45 N 0 40 0 35 0 35 50 25 0 25 50 75 100 125 150 50 25 0 25 50 75 100 125 150 TEMPERATURE C TEMPERATURE C Figure 23 Supply Current versus Temperature Figure 24 Supply Current versus Temperature NCP1050 1 2 NCP1053 4 5 0 48 0 21 0 47 0 20 lt 0 19 0 46 E z 0 18 0 45 a 0 17 5 0 44 0 16 gt amp 0 15 0 43 a a 0 14 0 42 0 13 0 41 0 12 50 25 0 25 50 75 100 125 150 50 25 0 25 50 75 100 125 150 TEMPERATURE C TEMPERATURE C Figure 25 Supply Current When Switching Figure 26 Supply Current in Fault Condition Disable versus Temperature versus Temperature 14 0 r r r r 13 9 CONDITION i Vcc pin 1 uF to ground 13 8 Control pin open E 137 Drain pin 1 kQ to Power Supply Increase Voltage Until Switching SUPPLY VOLTAGE V 50 25 0 25 50 TEMPERATURE C 75 Figure 27 Supply Voltage versus Temperature http onsemi com 13 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 OPERATING DESCRIPTION Introduction The NCP105X series represents a new higher level of integration by providing on a single monolithic chip all of the active power control logic and protection circuitry required to implement a high voltage
4. Control Input 2 Oscillator amp Gating Logic _ o e e s o AC Line kd Snubber n Input ES Converter A A DC Output O e i e id Power Switch Circuit Output 5 pM i Sate ee ee We eee Vcc Startup amp Voc de 1 Regulator Circuit l n Power Fault Detector E Switch A i pa Circuit pH Figure 1 Typical Application Pin Function Description Pin Pin SOT 223 DIP 8 Description 1 1 Voc This is the positive supply voltage input During startup power is supplied to this input from Pin 5 When Vcc reaches Vcc on the Startup Circuit turns off and the output is allowed to begin switching with 1 0 V hysteresis on the Vcc pin The capacitance connected to this pin programs fault timing and frequency modulation rate Control Input The Power Switch Circuit is turned off when a current greater than approximately 50 uA is drawn out of or applied to this pin A 10 V clamp is built onto the chip to protect the device from ESD damage or overvoltage conditions ERN This pin is the control circuit and Power Switch Circuit ground It is part of the integrated circuit lead frame e MEME Power Switch This pin is designed to directly drive the converter transformer primary and internally Drain connects to Power Switch and Startup Circuit http onsemi com 2 NCP1050 NCP1051 NCP1052
5. NCP1053 NCP1054 NCP1055 o_ M gt O AC Line 1 M Snubber y Input mE TA Zz Converter der d DC Output or d e s Power Switch Circuit Output Voc Startup e Startup Vec Reg Circuit artup TR 10V Es J gt a Fault Internal Detector Bias Voc Bypass 7 5 8 5 V gt Fault Timing A E Fault m Vco Sweep Latch Control Undervoltage nigra Switch Lockout Shutdown Q Circuit Ni R Driver e 45V Vcc SE i Oscillator lp 10 uA Turn On 48 pA Os M Latch pa Turn Off R Latch gt Q Ck 26V S Q mo Control R Input DAD 10V 4 Leading Edge 7 pa s Blanking e 3 3 V Current Limit x uum Comparator Da Turm J RSENSE 1444 Y pied Ground Figure 2 Representative Block Diagram http onsemi com 3 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 fosc high Oscillator Duty Cycle Oscillator Clock A75UA 375uA T IGONTROL SINK 0 uA Leading Edge On Duty Cycle Off Leading Edge On Leading Edge On I Duty Cycle Off pt No Se
6. 0 2 5 75 100 125 150 TEMPERATURE C OSCILLATOR FREQUENCY kHz Figure 7 Oscillator Frequency C Suffix versus Temperature 77 6 77 4 MAXIMUM DUTY CYCLE 50 25 0 25 50 75 100 125 150 TEMPERATURE C Figure 9 Maximum Duty Cycle versus Temperature OSCILLATOR FREQUENCY kHz FREQUENCY SWEEP kHz SINK CONTROL CURRENT THRESHOLD uA co 00 o o co A 92 50 25 0 25 TEMPERATURE C 50 75 100 125 150 Figure 6 Oscillator Frequency B Suffix versus Temperature 13 6 kHz 100 kHz NM wo A Ao O NO CO 44 kHz A o 50 25 0 25 50 75 TEMPERATURE C 100 125 150 Figure 8 Frequency Sweep versus Temperature 55 50 CURRENT RISING 45 40 CURRENT FALLING 50 25 0 2 TEMPERATURE C 5 50 75 Figure 10 Lower Window Control Input Current Thresholds versus Temperature http onsemi com 10 SOURCE CONTROL CURRENT THRESHOLD uA CLAMP VOLTAGE V LEAKAGE CURRENT uA NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055
7. 80 Switching Characteristics RL 50 Q Vps set for Ip 0 7 lim Turn on Time 90 to 10 Turn off Time 10 to 90 CURRENT LIMIT AND THERMAL PROTECTION Current Limit Threshold Ty 25 C Note 6 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 Conversion Power Deviation Ty 25 C Note 7 mA 100 107 200 214 300 321 400 428 530 567 680 728 Propagation Delay Current Limit Threshold to Power Switch Circuit Output NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 Thermal Protection Vcc 8 6 V Note 3 4 5 Shutdown Junction Temperature Increasing Hysteresis Junction Temperature Decreasing STARTUP CONTROL Startup Vcc Regulation Startup Threshold Vcc Regulation Peak Vcc Increasing Minimum Operating Vcc Valley Voltage After Turn On Hysteresis Undervoltage Lockout Threshold Voltage Voc Decreasing Startup Circuit Output Current Power Switch Circuit Output 40 V Voc 20V Ty 25 C Ty 40 to 125 C Voc Vecion 0 2 V Ty 25 C Ty 40 to 125 C Minimum Start up Drain Voltage Istart 0 5 MA Voc Vcc on 0 2 V Output Fault Condition Auto Restart Vcc Capacitor 10 uF Power Switch Circuit Output 40 V Average Switching Duty Cycle Frequency e Tested junction temperature range for the NCP105X series Tiow 40 C Thigh 125 C Maximum package power dissipation limits must be observed Guaranteed by design only Adjust di dt to reach Ijim in 4 0 u
8. NCP1055 Board Graphics NCP1050 Series Bottom View Figure 40 Printed Circuit Board and Component Layout http onsemi com 21 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 DEVICE ORDERING INFORMATION Note 10 Rps on lpk Package 2 mA NCP1052PZZZ DIP 8 NCP1053PZZZ CASE 626A NCP1054PZZZ NCP1055PZZZ 50 Units Rail SOT 223 CASE 318E 4000 Units Tape amp Reel NCP1055STZZZT3 10 Consult factory for additional optocoupler fail safe latching frequency current limit and line input options 11 ZZZ 44 100 or 136 for different frequency options http onsemi com 22 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 PACKAGE DIMENSIONS DIP 8 P SUFFIX CASE 626A 01 ISSUE O loan f TIT A N 1 hp K H G S 0 13 0 005 09 T A 0 B SOT 223 ST SUFFIX CASE 318E 04 ISSUE K A Ec EM LE EIN S B DUO t mmm L G ka A J bag e L d 0 08 0003 A i A M LI http onsemi com 23 NOTES 1 DIMENSIONING AND TOLERANCING PER ANSI Y14 5M 1982 2 CONTROLLING DIMENSION MILLIMETER 3 PACKAGE CONTOUR OPTIONAL ROUND OR SQUARE CORNERS 4 DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL 5 DIMENSIONS A AND B ARE DATUMS MILLIMETERS INCHES DIM MIN MAX MIN MAX A 9 40 10 16 0 370 0 400 B 6 10
9. a wide range of line input voltage and load current values The charger application transitions to a constant current output if the load current is increased beyond a preset range This can be very effective for battery charger application for portable products such as cellular telephones personal digital assistants and pagers Using the NCP105X series in applications such as these offers a wide range of flexibility for the system designer The NCP105X application offers a low cost alternative to other applications It uses a Dynamic Self Supply DSS function to generate its own operating supply voltage such that an auxiliary transformer winding is not needed It also offers the flexibility to override this function with an auxiliary winding if ultra low standby power is the designer s main concern This product also provides for automatic output overload short circuit and open loop protection by entering a programmable duty cycle burst mode of operation This eliminates the need for expensive devices overrated for power dissipation or maximum current or for redundant feedback loops The application shown in Figure 28 can be broken down into sections for the purpose of operating description Components C1 L1 and C6 provide EMI filtering for the design although this is very dependent upon board layout component type etc D1 through D4 along with C2 provide the AC to bulk DC rectification The NCP1053 drives the primary side of the trans
10. and normal operation of the converter are shown in Figure 3 Fault Detector The NCPIOSX series has integrated Fault Detector circuitry for detecting application fault conditions such as open loop overload or a short circuited output A timer is generated by driving the supply capacitor with a known current and hysteretically regulating the supply voltage between set thresholds The timer period starts when the supply voltage reaches the nominal upper threshold of 8 5 V and stops when the drain current of the integrated circuit draws the supply capacitor voltage down to the undervoltage lockout threshold of 7 5 V If during this timer period no feedback has been applied to the control input the fault detect logic is set to indicate an abnormal condition This may occur for example when the optocoupler fails or the output of the application is overloaded or completely shorted In this case the part will stop switching go into a low power mode and begin to draw down the supply capacitor to the reset threshold voltage of 4 5 V At that time the startup circuit will turn on again to drive the supply to the turn on threshold Then the part will begin the cycle again effectively sampling the control input to determine if the fault condition has been removed This mode is commonly referred to as burst mode operation and is shown is Figure 4 Proper selection of the supply capacitor allows successful startup with monotonically increasing out
11. flyback converter and compliance with very low standby power requirements for modern consumer electronic power supplies This device series is designed for direct operation from a rectified 240 VAC line source and requires minimal external components for a complete cost sensitive converter solution Potential markets include cellular phone chargers standby power supplies for personal computers secondary bias supplies for microprocessor keep alive supplies and IR detectors A description of each of the functional blocks is given below and the representative block diagram is shown in Figure 2 This device series features an active startup regulator circuit that eliminates the need for an auxiliary bias winding on the converter transformer fault logic with a programmable timer for converter overload protection unique gated oscillator configuration for extremely fast loop response with double pulse suppression oscillator frequency dithering with a controlled slew rate driver for reduced EMI cycle by cycle current limiting input undervoltage lockout with hysteresis thermal shutdown and auto restart or latched off fault detect device options These devices are available in economical 8 pin PDIP and 4 pin SOT 223 packages Oscillator The Oscillator is a unique fixed frequency duty cycle controlled oscillator It charges and discharges an on chip timing capacitor to generate a precise square wave signal used to pulse width modulate t
12. 133 penowey 9 pue suld NIGGOU OZOLTASL FYOD eouejonpu ANewng HW pz L 210 10 paubisag dv5 USIUI 8 pue SUId HEJS pue Z sulg WW Qr 0 JO SUINI G AUYONO9IS USIUI G Uld HEIS y Uld DMV 62 JO SUINI 76 AUVINIYd 87ESITCOXLO LUVd SHIDOIONHOAL DINOHLO373 H3dOOO LI A E MOZE MOTO door ES 84 LU 99 4 T e 9 X00z d SI su LEVIL TOGENG R 9l LO mch chch e Gee 8ESO0LdON cc 0 9 e LOLO LOL es ozz 0 E OLY E10 i pe ge 9007NL 0L ozz HOU i L va e c co WOZ vu di O9LENIN 29 22 sq y 4 4 p VSL9 HAS fe 900PNL OI eq ESS Lo 1072 es FARA ilo A sg SB 9u Ly ed UA e b HWOL cu gt e See e dol y 16 900 N1 n A Ges dos gt vou id e vO lt SN po Hig ZZ8SN HE 9007NI voz z1 9a Ig E Figure 28 Universal Input 6 5 Watt Converter Charger Application http onsemi com 17 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 Line Regulation Vin 85 265 Vac lout 120 mA 2mV lout 600 MA 1mV lout 1 2 A Vin 85 265 Vac lout 100 mA lout 500 MA lout 1 00 A Load Regulation Vin 85 Vac lout 120 mA 1 2 A Vin 110 Vac lout 120 mA 1 2 A Vin 230 Vac lout 120 MA 1 2 A Vin 265 Vac lout 120 MA 1 2 A Vin 85 Vac lout 100 MA 1 00 A Vin 110 Vac lout 100 MA 1 00 A
13. 2 0 Oz Printed Circuit Copper Clad 0 36 Sq Inch 1 0 Sq Inch 40 to 150 65 to 150 1 Maximum Ratings are those values beyond which damage to the device may occur Exposure to these conditions or conditions beyond those indicated may adversely affect device reliability Functional operation under absolute maximum rated conditions is not implied Functional operation should be restricted to the Recommended Operating Conditions A This device series contains ESD protection and exceeds the following tests Pins 1 3 Human Body Model 2000 V per MIL STD 883 Method 3015 Machine Model Method 400 V Pin 5 Human Body Model 1000 V per MIL STD 883 Method 3015 Machine Model Method 400 V Pin 5 is connected to the power switch and start up circuits and is rated only to the max voltage of the part or 700 V B This device contains Latch up protection and exceeds 100 mA per JEDEC Standard JESD78 http onsemi com 6 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 ELECTRICAL CHARACTERISTICS Vcc 8 0 V for typical values Ty 25 C for min max values Ty is the operating junction temperature range that applies Note 2 unless otherwise noted Characteristics Symbol Min Typ Max Unit OSCILLATOR Frequency Vcc 7 5 V fosc low Ty 25 C A Suffix Device B Suffix Device C Suffix Device Ty Tiow to Thigh A Suffix Device B Suffix Device C Suffix Device Frequency Vcc 8 5 V fosc high Ty 25 C
14. 5 Vac E E gt O O y 4 FE Vin 110 Vac Vin 230 Vac 0 0 0 5 1 1 5 2 0 0 5 1 0 1 5 LOAD CURRENT A LOAD CURRENT A Figure 32 Converter Load Regulation Figure 33 Charger Load Regulation Tee Bal Single Se des pag Tee BET Single fan Ok lie Trete E ANT Ch1 Vout Chi V h2 lout 0 2 A di out AD vw n Ch2 lout 0 2 A div n Vin 230 Vac am mH Er TV EC TUS es TET nog EHI LUCR ge TO onn RA 083 Dine Figure 34 Converter Load Transient Response Figure 35 Charger Load Transient Response http onsemi com 19 EFFICIENCY 75 70 65 60 55 50 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 Vin 110 Vac Vin 85 Vac _ Vin 230 Vac Vin 265 Vac EFFICIENCY 70 Vin 85 Vac 65 m Vin 110 Vac 60 55 0 Vac Vin 265 Vac 50 45 0 0 5 1 0 1 5 0 0 5 1 0 LOAD CURRENT A LOAD CURRENT A Figure 36 Converter Efficiency Figure 37 Charger Efficiency Tee MET Mingle 5e Soi BAs I Tee BE Single San TOD fie I ii 4 li 1 ly Ch1 Vout Ch1 Vout Ch2 Rectified Vin Ch2 Rectified Vin Vin 230 Vac Vin 230 Vac lout 0 5 A PRE J lout 0 5 A ur ut END uv xou AE ULI erre erre Figure 38 Converter On Off Line Transient Figure 39 Charger On Off Line Transient Response Response http onsemi com 20 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054
15. 6 60 0 240 0 260 C 3 94 445 0 155 0 175 D 0 38 0 51 0 015 0 020 F 1 02 1 78 0 040 0 070 G 2 54 BSC 0 100 BSC H 0 76 1 27 0 030 0 050 J 0 20 0 30 0 008 0 012 K 2 92 3 43 0 115 0 135 L 7 62 BSC 0 300 BSC M 10 10 N 0 76 1 01 0 030 0 040 NOTES 1 DIMENSIONING AND TOLERANCING PER ANSI Y14 5M 1982 2 CONTROLLING DIMENSION INCH INCHES MILLIMETERS MIN MAX MIN MAX 0 249 0 263 6 30 6 70 0 130 0 145 3 30 3 70 0 060 0 068 1 50 1 75 0 024 0 035 0 60 0 89 0 115 0 126 2 90 3 20 0 087 0 094 2 20 2 40 0 0008 10 0040 0 020 0 100 0 009 0 014 0 24 0 35 0 060 0 078 1 50 2 00 0 033 0 041 0 85 1 05 0 10 0 9 10 0 264 0 287 6 70 7 30 o raczo oo w 3 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 The products described herein NCP1050 1051 1052 1053 1054 1055 may be covered by one or more of the following U S patents 4 553 084 5 418 410 5 477 175 6 137 696 6 137 702 6 271 735 6 480 043 6 362 067 6 587 357 There may be other patents pending SENSEFET is a trademark of Semiconductor Components Industries LLC SCILLC ON Semiconductor and TM are registered trademarks of Semiconductor Components Industries LLC SCILLC SCILLC reserves the right to make changes without further notice to any products herein SCILLC makes no warranty representation or guarantee regarding the suitability of its pr
16. A Suffix Device B Suffix Device C Suffix Device Ty Tiow to Thigh A Suffix Device B Suffix Device C Suffix Device Frequency Sweep Vcc 7 5 V to 8 5 V Ty 25 C Maximum Duty Cycle CONTROL INPUT Lower Window Input Current Threshold Switching Enabled Sink Current Increasing Switching Disabled Sink Current Decreasing Upper Window Input Current Threshold Switching Enabled Source Current Increasing Switching Disabled Source Current Decreasing Control Window Input Voltage V Lower Isink 25 uA Viow 1 1 1 35 1 6 Upper Isource 25 uA Vhigh 4 2 4 6 5 0 2 Tested junction temperature range for the NCP105X series Tiow 40 C Thigh 125 C http onsemi com 7 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 ELECTRICAL CHARACTERISTICS Vcc 8 0 V for typical values Ty 25 C for min max values Ty is the operating junction temperature range that applies Note 3 unless otherwise noted meritos ove Wm mw we Unit POWER SWITCH CIRCUIT Power Switch Circuit On State Resistance Rps on Q NCP1050 NCP1051 NCP1052 Ip 50 mA Ty 25 C ai 22 30 Ty 125 C 42 55 NCP1053 NCP1054 NCP1055 Ip 100 mA Ty 25 C 10 15 Tj 125 C 23 28 Power Switch Circuit amp Startup Breakdown Voltage V BR DS 700 V Ip ort 100 uA Ta 25 C Power Switch Circuit amp Startup Circuit Off State Leakage Current Ips ott uA Vos 650 V Ty 25 C 25 40 Ty 125 C 15
17. I I Leading Edge On Current Limit Off I I Power Switch Circuit Gate Drive Current Limit Threshold Primary Current Current Limit lt Propagation Delay Figure 3 Timing Diagram for Gated Oscillator with Dual Edge PWM http onsemi com 4 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 lcc1 Current Measurement lec2 Current Measurement Vecion EN Hysteretic Regulation VcC off Y Voc VcCtreset la lcca Current Measurement OV 6 3 MA start 0mA lcc1 i Icc CC2 loca 0mA l start A7 _ ZA e A A ICONTROL SINK BN il OLA V pin 5 S LE 4 LA Fault Applied Fault Removed Figure 4 Non Latching Fault Condition Timing Diagram http onsemi com 5 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 MAXIMUM RATINGS Note 1 Power Switch and Startup Circuit Drain Voltage Range 0 3 to 700 Drain Current Peak During Transformer Saturation 2 0 lim Max Power Supply Vcc Bypass and Control Input Voltage Range 0 3 to 10 Current 100 Thermal Characteristics P Suffix Plastic Package Case 626A 01 Junction to Lead Junction to Air 2 0 Oz Printed Circuit Copper Clad 0 36 Sq Inch 1 0 Sq Inch ST Suffix Plastic Package Case 318E 04 Junction to Lead Junction to Air
18. O O NCP1050P100 O O NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 Monolithic High Voltage Gated Oscillator Power Switching Regulator The NCP1050 through NCP1055 are monolithic high voltage regulators that enable end product equipment to be compliant with low standby power requirements This device series combines the required converter functions allowing a simple and economical power system solution for office automation consumer and industrial products These devices are designed to operate directly from a rectified AC line source In flyback converter applications they are capable of providing an output power that ranges from 6 0 W to 40 W with a fixed AC input of 100 V 115 V or 230 V and 3 0 W to 20 W with a variable AC input that ranges from 85 V to 265 V This device series features an active startup regulator circuit that eliminates the need for an auxiliary bias winding on the converter transformer fault detector and a programmable timer for converter overload protection unique gated oscillator configuration for extremely fast loop response with double pulse suppression power switch current limiting input undervoltage lockout with hysteresis thermal shutdown and auto restart fault detection These devices are available in economical 8 pin dual in line and 4 pin SOT 223 packages Features e Startup Circuit Eliminates the Need for Transformer Auxiliary Bias Winding e Optional Auxiliary Bias Winding Override for Lowes
19. Vin 230 Vac lout 100 mA 1 00 A Vin 265 Vac lout 100 MA 1 00 A Output Ripple Vin 110 Vac lou Vin 230 Vac lou Vin 110 Vac lou Vin 230 Vac lou Efficiency Vin 110 Vac lou Vin 230 Vac lout Vin 110 Vac Rg Vin 230 Vac Rg l Vin 110 Vac Rg 0 Q lout 1 00 A Vin 230 Vac Rg 0 Q lout 1 00 A No Load Input Power Vin 110 Vac lout 0 A Vin 230 Vac lout 0 A Standby Output Power Vin 110 Vac Pin 1 W Vin 230 Vac Pin 1W Short Circuit Load Input Power Vin 110 Vac Vout 0 V Shorted Vin 230 Vac Vout 0 V Shorted Vin 110 Vac Rg 1 2 Q Vout 0 V Shorted Vin 230 Vac Rg 1 2 Vout 0 V Shorted Vin 110 Vac Rg 0 Q Vout 0 V Shorted Vin 230 Vac Rg 00 Vout 0 V Shorted Figure 29 Converter and Charger Test Data Summary http onsemi com 18 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 5 23 5 22 2521 lout 100 MA 2 L 5 20 2 x 5 19 gt 5 18 5 a 9e lout 500 mA 5 16 5 15 lout 1 A 5 14 80 130 180 230 280 80 130 180 230 280 LINE INPUT VOLTAGE Vac LINE INPUT VOLTAGE Vac Figure 30 Converter Line Regulation Figure 31 Charger Line Regulation 6 6 5 5 LU LU S H 5 O 3 Q 3 Vin 265 Vac 5 E Vin 8
20. former and the capacitor C5 is an integral part of the Dynamic Self Supply R1 C3 and D5 comprise an RCD snubber and R2 and C4 comprise a ringing damper both acting together to protect the IC from voltage transients greater than 700 volts and reduce radiated noise from the converter Diode D6 along with C7 9 L2 C11 and C12 rectify the transformer secondary and filter the output to provide a tightly regulated DC output IC3 is a shunt regulator that samples the output voltage by virtue of R5 and R6 to provide drive to the optocoupler IC2 Light Emitting Diode LED C10 is used to compensate the shunt regulator When the application is configured as a Charger Q1 delivers additional drive to the optocoupler LED when in constant current operation by sampling the output current through R7 and R8 Component Selection Guidelines Choose snubber components R1 C3 and D5 such that the voltage on pin 5 is limited to the range from 0 to 700 volts These components protect the IC from substrate injection if the voltage was to go below zero volts and from avalanche if the voltage was to go above 700 volts at the cost of slightly reduced efficiency For lower power design a simple RC snubber as shown or connected to ground can be sufficient Ensure that these component values are chosen based upon the worst case transformer leakage inductance and worst case applied voltage Choose R2 and C4 for best performance radiated switching noise Ca
21. he Power Switch Circuit During the discharge of the timing capacitor the Oscillator duty cycle output holds one input of the Driver low This action keeps the Power Switch Circuit off thus limiting the maximum duty cycle A frequency modulation feature is incorporated into the IC in order to aide in EMI reduction Figure 3 illustrates this frequency modulation feature The power supply voltage Vcc acts as the input to the built in voltage controlled oscillator As the Vcc voltage is swept across its nominal operating range of 7 5 to 8 5 V the oscillator frequency is swept across its corresponding range The center oscillator frequency is internally programmed for 44 kHz 100 kHz or 136 kHz operation with a controlled charge to discharge current ratio that yields a maximum Power Switch duty cycle of 77 The Oscillator temperature characteristics are shown in Figures 5 through 9 Contact an ON Semiconductor sales representative for further information regarding frequency options Control Input The Control Input pin circuit has parallel source follower input stages with voltage clamps set at 1 35 and 4 6 V Current sources clamp the input current through the followers at approximately 47 5 uA with 10 uA hysteresis When a source or sink current in excess of this value is applied to this input a logic signal generated internally changes state to block power switch conduction Since the output of the Control Input sense is sampled contin
22. n Latch over an ordinary Gated Oscillator allows a faster load transient response The power switch is allowed to turn on immediately within the maximum duty cycle time period when the control input signals a necessary change in state Turn Off Latch A Turn Off Latch feature has been incorporated into this device series to protect the power switch circuit from excessive current and to reduce the possibility of output overshoot in reaction to a sudden load removal If the Power Switch current reaches the specified maximum current limit the Current Limit Comparator resets the Turn Off Latch and turns the Power Switch Circuit off The turn off latch is also reset when the Oscillator output signal goes low or the Control Input is asserted thus terminating output MOSFET conduction Because of this response to control input signals it provides a very fast transient response and very tight load regulation The turn off latch has an edge triggered set input which ensures that the switch can only be activated once during any oscillator period This is commonly referred to as double pulse suppression http onsemi com 14 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 Current Limit Comparator and Power Switch Circuit The Power Switch Circuit is constructed with a SENSEFET in order to monitor the drain current A portion of the current flowing through the circuit goes into a sense element Rsense The current limit comparator detect
23. oducts for any particular purpose nor does SCILLC assume any liability arising out of the application or use of any product or circuit and specifically disclaims any and all liability including without limitation special consequential or incidental damages Typical parameters which may be provided in SCILLC data sheets and or specifications can and do vary in different applications and actual performance may vary over time All operating parameters including Typicals must be validated for each customer application by customer s technical experts SCILLC does not convey any license under its patent rights nor the rights of others SCILLC products are not designed intended or authorized for use as components in systems intended for surgical implant into the body or other applications intended to support or sustain life or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application Buyer shall indemnify and hold SCILLC and its officers employees subsidiaries affiliates and distributors harmless against all claims costs damages and expenses and reasonable attorney fees arising out of directly or indirectly any claim of personal injury or death associated with such unintended or unauthorized use even if such claim alleges that SCILLC was negligent regarding the design or man
24. pacitor C5 serves multiple purposes It is used along with the internal startup circuitry to provide power to the IC in lieu of a separate auxiliary winding It also serves to provide timing for the oscillator frequency sweep for limiting the conducted EMI emissions The value of C5 will also determine the response during an output fault overload or short circuit or open loop condition as shown in Figure 4 along with the total output capacitance Resistors R5 and R6 will determine the regulated output voltage along with the reference voltage chosen with IC3 The base to emitter voltage drop of Q1 along with the value of R7 will set the fixed current limit value of the Charger application R9 is used to limit the base current of Q1 Component R8 can be selected to keep the current limit fixed with very low values of output voltage or to provide current limit foldback with results as shown in Figures 29 and 33 A relatively large value of R8 allows for enough output voltage to effectively drive the optocoupler LED for fixed current limit A low value of R8 along with resistor R10 provides for a low average output power using the fault protection feature when the output voltage is very low C13 provides for output voltage stability when the Charger application is in current limit http onsemi com 16 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 1ndino 464842 104 vi 0 Z 01 py ebueyo pue OLY ZY pue ELO LO PPY 6
25. put voltage without falsely sensing a fault condition Figure 4 shows successful startup and the evolution of the signals involved in the presence of a fault Thermal Shutdown The internal Thermal Shutdown block protects the device in the event that the maximum junction temperature is exceeded When activated typically at 160 C one input of the Driver is held low to disable the Power Switch Circuit The Power Switch is allowed to resume operation when the junction temperature falls below 85 C The thermal shutdown feature is provided to prevent catastrophic device failures from accidental overheating It is not intended to be used as a substitute for proper heatsinking http onsemi com 15 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 APPLICATIONS Two application examples have been provided in this document and they are described in detail in this section Figure 28 shows a Universal Input 6 Watt Converter Application as well as a 5 5 Watt Charger Application using the NCP1053B The Charger consists of the additional components Q1 C13 and R7 through R10 as shown These were constructed and tested using the printed circuit board layout shown in Figure 40 The board consists of a fiberglass epoxy material FR4 with a single side of two ounce per square foot 70 um thick copper foil Test data from the two applications is given in Figures 29 through 39 Both applications generate a well regulated output voltage over
26. s if the voltage across Rsense exceeds the reference level that is present at its inverting input If this level is exceeded the comparator quickly resets the Turn Off Latch thus protecting the Power Switch Circuit A Leading Edge Blanking circuit was placed in the current sensing signal path to prevent a premature reset of the Turn Off Latch A potential premature reset signal is generated each time the Power Switch Circuit is driven into conduction and appears as a narrow voltage spike across current sense resistor Rgense The spike is due to the Power Switch Circuit gate to source capacitance transformer interwinding capacitance and output rectifier recovery time The Leading Edge Blanking circuit has a dynamic behavior that masks the current signal until the Power Switch Circuit turn on transition is completed The current limit propagation delay time is typically 135 to 165 nanoseconds This time is measured from when an overcurrent appears at the Power Switch Circuit drain to the beginning of turn off Care must be taken during transformer saturation so that the maximum device current limit rating is not exceeded The high voltage Power Switch Circuit is monolithically integrated with the control logic circuitry and is designed to directly drive the converter transformer Because the characteristics of the power switch circuit are well known the gate drive has been tailored to control switching transitions to help limit electromagne
27. sec Noro http onsemi com 8 Consult factory for additional options including test and trim for output power accuracy NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 ELECTRICAL CHARACTERISTICS Vcc 8 0 V for typical values Ty 25 C for min max values Ty is the operating junction temperature range that applies Note 8 unless otherwise noted Characteristics Symbol Min Typ Max Unit TOTAL DEVICE Power Supply Current After UVLO Turn On Note 9 mA Power Switch Circuit Enabled loci NCP1050 NCP1051 NCP1052 A Suffix Device 0 35 0 45 0 55 B Suffix Device 0 40 0 50 0 60 C Suffix Device 0 40 0 525 0 65 NCP1053 NCP1054 NCP1055 A Suffix Device 0 40 0 50 0 60 B Suffix Device 0 45 0 575 0 70 C Suffix Device 0 50 0 65 0 80 Power Switch Circuit Disabled Non Fault Condition lec2 0 35 0 45 0 55 Fault Condition lcca 0 10 0 175 0 25 8 Tested junction temperature range for the NCP105X series Tiow 40 C Thigh 1 25 C 9 See Non Latching Fault Condition Timing Diagram in Figure 4 http onsemi com 9 NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055 46 T T T Voc VcC on OSCILLATOR FREQUENCY kHz A ww 50 25 0 25 50 75 100 125 150 TEMPERATURE C Figure 5 Oscillator Frequency A Suffix versus Temperature 142 140 138 136 134 132 130 128 126 124 50 25
28. t Standby Power Applications Converter Output Overload and Open Loop Protection Auto Restart Fault Protection IC Thermal Fault Protection Unique Dual Edge Gated Oscillator Configuration for Extremely Fast Loop Response Oscillator Frequency Dithering with Controlled Slew Rate Driver for Reduced EMI e Low Power Consumption Allowing European Blue Angel Compliance e On Chip 700 V Power Switch Circuit and Active Startup Circuit Rectified AC Line Source Operation from 85 V to 265 V e Input Undervoltage Lockout with Hysteresis e Oscillator Frequency Options of 44 kHz 100 kHz 136 kHz Typical Applications e AC DC Converters e Wall Adapters e Portable Electronic Chargers e Low Power Standby and Keep Alive Supplies O Semiconductor Components Industries LLC 2003 1 July 2003 Rev 7 ON Semiconductor http onsemi com MARKING DIAGRAMS DIP 8 CASE 626A P SUFFIX 4 Pin 1 Voc 2 Control Input 3 7 8 Ground 4 No Connection 5 Power Switch Drain 4 SOT 223 y CASE 318E 1 ST SUFFIX Pin 1 V CC 2 Control Input 3 Power Switch Drain 4 Ground X Current Limit 0 1 2 3 4 5 Z Oscillator Frequency A B C A Assembly Location WL L Wafer Lot YY Y Year WW W Work Week ORDERING INFORMATION See detailed ordering and shipping information on page 22 of this data sheet Publication Order Number NCP1050 D NCP1050 NCP1051 NCP1052 NCP1053 NCP1054 NCP1055
29. tic interference EMI The Power Switch Circuit is capable of switching 700 V with an associated drain current that ranges nominally from 0 10 to 0 68 Amps Startup Circuit Rectified AC line voltage is applied to the Startup Circuit on Pin 5 through the primary winding The circuit is self biasing and acts as a constant current source gated by control logic Upon application of the AC line voltage this circuit routes current into the supply capacitor typically connected to Pin 1 During normal operation this capacitor is hysteretically regulated from 7 5 to 8 5 V by monitoring the supply voltage with a comparator and controlling the startup current source accordingly This Dynamic Self Supply DSS functionality offers a great deal of applications flexibility as well The startup circuit is rated at a maximum 700 V maximum power dissipation limits must be observed Undervoltage Lockout An Undervoltage Lockout UVLO comparator is included to guarantee that the integrated circuit has sufficient voltage to be fully functional The UVLO comparator monitors the supply capacitor input voltage at Pin and disables the Power Switch Circuit whenever the capacitor voltage drops below the undervoltage lockout threshold When this level is crossed the controller enters a new startup phase by turning the current source on The supply voltage will then have to exceed the startup threshold in order to turn off the startup current source Startup
30. ufacture of the part SCILLC is an Equal Opportunity Affirmative Action Employer PUBLICATION ORDERING INFORMATION Literature Fulfillment JAPAN ON Semiconductor Japan Customer Focus Center Literature Distribution Center for ON Semiconductor 2 9 1 Kamimeguro Meguro ku Tokyo Japan 153 0051 P O Box 5163 Denver Colorado 80217 USA Phone 81 3 5773 3850 Phone 303 675 2175 or 800 344 3860 Toll Free USA Canada on a Fax 303 675 2176 or 800 344 3867 Toll Free USA Canada ON Semiconductor e com Email orderlit onsemi com For additional information please contact your local N American Technical Support 800 282 9855 Toll Free USA Canada did NCP1050 D
31. uously during ton 77 duty cycle it is possible to turn the Power Switch Circuit on or off at any time within ton Because it does not have to wait for the next cycle rising edge of the clock signal to switch on and because it does not have to wait for current limit to turn off the circuit has a very fast transient response as shown in Figure 3 In a typical converter application the control input current is drawn by an optocoupler The collector of the optocoupler is connected to the Control Input pin and the emitter is connected to ground The optocoupler LED is mounted in series with a shunt regulator typically a TL431 at the DC output of the converter When the power supply output is greater than the reference voltage shunt regulator voltage plus optocoupler diode voltage drop the optocoupler turns on pulling down on the Control Input The control input logic is configured for line input sensing as well Turn On Latch The Oscillator output is typically a 77 positive duty cycle square waveform This waveform is inverted and applied to the reset input of the turn on latch to prevent any power switch conduction during the guaranteed off time This square wave is also gated by the output of the control section and applied to the set input of the same latch Because of this gating action the power switch can be activated when the control input is not asserted and the oscillator output is high The use of this unique gated Turn O
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