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ANALOG DEVICES ADP2105/ADP2106/ADP2107 handbook

1. 100 100 Vin 3 6V 95 95 Vin 2 7V 90 Vin 2 7V 90 85 3 6V 85 g Vin 4 2 gt 80 Vin 5 5 75 Vin 4 2V 2 75 o o 70 70 ui Vin 5 5V 65 65 60 60 INDUCTOR 5012 1 29H INDUCTOR 621 1 59H 2 DCR 7 B 55 DCR 21mO S TA 25 C 5 25 C 5 50 50 8 1 10 100 1000 10000 1 10 100 1000 10000 LOAD CURRENT mA LOAD CURRENT mA Figure 10 Efficiency ADP2107 1 2 V Figure 13 Efficiency ADP2107 1 8 V 1 23 2 7V 40 C 2 7V 25 C 27V 125 3 6V 40 3 6V 25 3 6 125 5 5 40 C 5 5V 25 5 5 125 1 22 1 21 E b E g 5 o ELEM 2 rh n 5 119 o 1 18 INDUCTOR 5028 2 5uH 5 g DCR 13mO 25 3 S 5 1 17 8 1 10 100 1000 10000 0 01 01 1 10 100 1000 10000 LOAD CURRENT mA LOAD CURRENT mA Figure 11 Efficiency ADP2107 3 3 V Figure 14 Output Voltage Accuracy ADP2107 1 2 V 1 85 3 38 3 6 409 3 6V 25 3 6V 125 5 5 40 5 5 25 5 5V
2. Table 8 Inductor Recommendations for the ADP2105 ADP2106 ADP2107 Small Sized Inductors Large Sized Inductors Vendor 5mmx5mm 5mmx5mm Sumida CDRH2D14 3D16 CDRH4D18 4022 3D28 4D28 5D18 6D12 Toko 1069AS DB3018 D52LC D518LC 1098AS DE2812 D62LCB 1070AS DB3020 Coilcraft LPS3015 LPS4012 DO1605T DO3314 Cooper SD3110 SD3112 SD10 SD12 SD14 SD52 Bussmann SD3114 SD3118 SD3812 SD3814 Rev A Page 17 of 32 ADP2105 ADP2106 ADP2107 OUTPUT CAPACITOR SELECTION The output capacitor selection affects both the output voltage ripple and the loop dynamics of the converter For a given loop crossover frequency the frequency at which the loop gain drops to 0 dB the maximum voltage transient excursion overshoot is inversely proportional to the value of the output capacitor Therefore larger output capacitors result in improved load transient response To minimize the effects of the dc to dc converter switching the crossover frequency of the compensation loop should be less than 1 10 of the switching frequency Higher crossover frequency leads to faster settling time for a load transient response but it can also cause ringing due to poor phase margin Lower crossover frequency helps to provide stable operation but needs large output capacitors to achieve competitive overshoot specifications Therefore the optimal crossover frequency for the control loop of ADP2105 ADP2106 ADP2107
3. 2105 ANALOG DEVICES 1 Amp 1 5 Amp 2 Amp Synchronous Step Down DC to DC Converters ADP2105 ADP2106 ADP2107 FEATURES Extremely high 97 efficiency Ultralow quiescent current 20 pA 1 2 MHz switching frequency 0 1 pA shutdown supply current Maximum load current ADP2105 1A ADP2106 1 5 A ADP2107 2A Input voltage 2 7 V to 5 5 V Output voltage 0 8 V to Vin Maximum duty cycle 10096 Smoothly transitions into low dropout LDO mode Internal synchronous rectifier Small 16 lead 4 mm x 4 mm LFCSP VQ package Optimized for small ceramic output capacitors Enable shutdown logic input Undervoltage lockout Soft start APPLICATIONS Mobile handsets PDAs and palmtop computers Telecommunication networking equipment Set top boxes Audio video consumer electronics TYPICAL PERFORMANCE CHARACTERISTICS EFFICIENCY 75 GENERAL DESCRIPTION The ADP2105 ADP2106 ADP2107 are low quiescent current synchronous step down dc to dc converters in a compact 4 mm x 4 mm LFCSP VQ package At medium to high load currents these devices use a current mode constant frequency pulse width modulation PWM control scheme for excellent stability and transient response To ensure the longest battery life in portable applications the ADP2105 ADP2106 ADP2107 use pulse frequency modulation PFM control scheme under light load conditions that reduces switching frequency to save power
4. 700mA CH3 1 00A Q 10 00 CH3 1 00A Q E 10 00 OUTPUT CAPACITOR 22yF 4 7uF OUTPUT CAPACITOR 10 4 7 INDUCTOR CDRH5D18 4 1uH COMPENSATION RESISTOR 270kO COMPENSATION RESISTOR 135kO COMPENSATION CAPACITOR 39pF COMPENSATION CAPACITOR 82pF Figure 49 1 A Load Transient Response for ADP2105 3 3 Figure 52 1 A Load Transient Response for ADP2105 3 3 nents Chosen for 5 Overshoot with External Components Chosen for 10 Overshoot Rev A Page 21 of 32 INDUCTOR CDRH5D18 4 1uH 06079 089 06079 092 ADP2105 ADP2106 ADP2107 EFFICIENCY CONSIDERATIONS Efficiency is defined as the ratio of output power to input power The high efficiency of the ADP2105 ADP2106 ADP2107 has two distinct advantages First only a small amount of power is lost in the dc to dc converter package that reduces thermal constraints In addition high efficiency delivers the maximum output power for the given input power extending battery life in portable applications There are four major sources of power loss in dc to dc converters like the ADP2105 ADP2106 ADP2107 e switch conduction losses e Inductor losses Switching losses Transition losses Power Switch Conduction Losses Power switch conduction losses are caused by the flow of output current through the P channel power switch and the N channel synchronous rectifier which have internal resistances Rps on associated with them The amount of power loss
5. 6 Figure 30 Mode of Operation at Very Light Load 10 mA ww dzsc 06079 030 CH3 3 88V 06079 093 06079 083 Rev A Page 11 of 32 ADP2105 ADP2106 ADP2107 DE SWITCH OUTPUT VOLTAGE AC COUPLED INDUCTOR CURRENT 06079 033 50 400ns 3 88V CH3 2V CH4 200mAQ 17 4 Figure 31 DCM Mode of Operation at Light Load 100 mA LX NODE SWITCH NODE 06079 034 20 2us A CH3 1 84V CH3 27 1AQ 13 496 Figure 32 Minimum Off Time Control at Dropout LX NODE SWIT OUTPUT VOLTAGE AC COUPLED INDUCTOR CURRENT 8 20 1us CH3 3 88V CH3 2V CH4 1AQ 17 4 Figure 33 PWM Mode of Operation at Medium Heavy Load 1 5 A ADP2105 ADP2106 ADP2107 LX NODE SWITCH NODE CHANNE FREQUENCY 7 336 6kHz INDUCTOR CURRENT OUTPUT VOLTAGE 06079 032 06079 035 1V M 4us A CH3 1 8V 1V M 400 5 A 1 84V CH3 5V 1AQ 45 CH3 5V 500mAQ 20 2 Figure 34 Current Limit Behavior of ADP2107 Frequency Foldback Figure 35 Startup and Shutdown Waveform Css 1 nF SS Time 1 ms Rev A Page 12 of 32 Vx 1g E www dzsc ADP2105 ADP2106 ADP2107 THEORY OF OPERATION
6. OUTPUT VOLTAGE 1 8V CROSS INPUT VOLTAGE 3 60 FREQUENC LOAD CURRENT 1A INDUCTOR 2 2uH LPS4012 OUTPUT CAPACITOR 22pF 22 COMPENSATION RESISTOR 180kQ COMPENSATION CAPACITOR 56pF 1 10 kHz NOTES 100 1 EXTERNAL COMPONENTS WERE CHOSEN FOR A 5 OVERSHOOT FOR A 1A LOAD TRANSIENT ADP2105 OUTPUT VOLTAGE 1 2V LOAD CURRENT 1A INPUT VOLTAGE 3 6V INDUCTOR 3 3pH 503814 OUTPUT CAPACITOR 22yF 22uF 4 7uF COMPENSATION RESISTOR 267 COMPENSATION CAPACITOR 39pF 1 10 kHz NOTES 100 300 1 EXTERNAL COMPONENTS WERE CHOSEN FORA 5 OVERSHOOT FOR A 1A LOAD TRANSIENT www dzsc LOOP PHASE Degrees LOOP GAIN dB 06079 055 LOOP PHASE Degrees LOOP GAIN dB 06079 056 LOOP PHASE Degrees LOOP GAIN dB 06079 057 Rev A Page 20 of 32 60 50 40 30 20 ADP2105 LOOP PHASE OUTPUT VOLTAGE 1 2V INPUT VOLTAGE 5 5V LOAD CURRENT 1A INDUCTOR 3 3pH 503814 OUTPUT CAPACITOR 22yF 22uF 4 7uF ROSSOVER REQUENCY 79 COMPENSATION RESISTOR 267 COMPENSATION CAPACITOR 39pF 10 kHz NOTES 100 300 1 EXTERNAL COMPONENTS WERE CHOSEN FORA 5 OVERSHOOT FOR A 1A LOAD TRANSIENT ADP2107 LOOP PHAS CROSSOVER OUTPUT VOLTAGE 2 5V
7. 125 C 3 36 1 83 3 34 9 18 9 2334 3 30 gt gt 5 1 79 5 ot a 3 28 2 2 o o 3 26 1 77 2 7V 40 C 2 7 25C 2 7 125 _ 3 24 3 6V 40 C 3 6V 25 1 3 6V 125 C 3 8 5 5V 40 5 5V 25 5 5V 125 2 1 75 8 3 22 8 0 1 1 10 100 1000 10000 0 01 0 1 1 10 100 1000 0000 LOAD CURRENT mA LOAD CURRENT mA Figure 12 Output Voltage Accuracy ADP2107 1 8 V Figure 15 Output Voltage Accuracy ADP2107 3 3 V Rev A Page 8 of 32 www dzsc ADP2105 ADP2106 ADP2107 10000 1000 s E 25 40 E amp 100 8 5 4 z 5 x 2 1 o z E 10 n 1_ 125 E 8 H 8 8 1 8 08 12 16 20 24 28 32 36 40 44 48 52 27 30 33 36 39 42 45 48 51 54 INPUT VOLTAGE V INPUT VOLTAGE V m Figure 16 Quiescent Current vs Input Voltage Figure 19 Switch On Resistance vs Input Voltage ADP2105 0 802 0 801 0 800 y g 4 5 0 799 M o a gt NMOS SYNCHRONOUS RECTIF 0 798 x 3 5 0 797 5 Eu E z o 0 796 0 795 8 3 40 20 0 20 404 60 80 100 120125 27 30 33 36 39 42 45 48 51 54 TEMPERATURE C INPUT VOLTAGE V Figure 17 Feedback Voltage vs Temperature Figure 20 Switch On Resistance
8. NO CONNECT into account when calculating resistor values The FB bias current can be ignored for a higher divider string current but this degrades efficiency at very light loads To limit output voltage accuracy degradation due to FB bias current to less than 0 0596 0 596 maximum ensure that the divider string current is greater than 20 To calculate the desired resistor values first determine the value of the bottom divider string resistor Rsor by R Vip where Vrs 0 8 V the internal reference Isrrine is the resistor divider string current Viy INPUT VOLTAGE 2 7V TO 5 5V OUTPUT VOLTAGE 1 2V 1 5V 1 8V 3 3V Vour 06079 065 Figure 37 Typical Applications Circuit for Fixed Output Voltage Options ADP2105 ADP2106 ADP2107 xx Vin INPUT VOLTAGE 2 7V TO 5 5V OUTPUT VOLTAGE 0 8V TO Vin ADP2106 ADP2107 id NC NO CONNECT Figure 38 Typical Applications Circuit for Adjustable Output Voltage Option ADP2105 ADP2106 ADP2107 ADJ i fg e www dzsc GND ADP2105 PGNDG _ R i LOAD IHH FB 06079 038 Rev Page 16 of 32 ADP2105 ADP2106 ADP2107 Once Reor is determined calculate the value of the top resistor by Vour Vrs Vis Ryop ADP2105 ADP2106 ADP2107 xx where xx represents the fixed output voltage include the resistive voltage divider internally reducing the ext
9. The ADP2105 ADP2106 ADP2107 run from input voltages of 2 7 V to 5 5 V allowing single Li Li polymer cell multiple alkaline NiMH cells PCMCIA and other standard power sources The output voltage of ADP2105 ADP2106 ADP2107 ADJ is adjustable from 0 8 V to the input voltage whereas the ADP2105 ADP2106 ADP2107 xx are available in preset output voltage options of 3 3 V 1 8 V 1 5 V and 1 2 V Each of these variations is available in three maximum current levels 1 A ADP2105 1 5 A ADP2106 and 2 A ADP2107 The power switch and synchronous rectifier are integrated for minimal external part count and high efficiency During logic controlled shutdown the input is disconnected from the output and it draws less than 0 1 uA from the input source Other key features include undervoltage lockout to prevent deep battery discharge and programmable soft start to limit inrush current at startup TYPICAL OPERATING CIRCUIT ioo INPUT VOLTAGE 2 7V 5 5V 1k 10 OUTPUT VOLTAGE 2 5V 0 200 400 600 800 1000 1200 1400 1600 1800 2000 LOAD CURRENT mA 06079 002 Figure 1 Efficiency vs Load Current for the ADP2107 with Vour 2 5 V Figure 2 Circuit Configuration of ADP2107 with Vour 2 5 V Rev A Information furnished by Analog Devices is believed to be accurate and reliable However no responsibility is assumed by Analog Devices for its use nor for any infringements of paten
10. is 80 KHz 1 15 of the switching frequency For a crossover frequency of 80 kHz Figure 39 shows the maximum output voltage excursion during a 1A load transient as the product of the output voltage and the output capacitor is varied Choose the output capacitor based on the desired load transient response and target output voltage OVERSHOOT OF OUTPUT VOLTAGE MN oO 06079 070 a a w w a a a a a o a OUTPUT CAPACITOR x OUTPUT VOLTAGE uC Figure 39 96 Overshoot for a 1 A Load Transient Response vs Output Capacitor x Output Voltage For example if the desired 1 A load transient response overshoot is 596 for an output voltage of 2 5 V then from Figure 39 Output Capacitor x Output Voltage 50 uC gt Output Capacitor 2 20 uF The ADP2105 ADP2106 ADP2107 have been designed for operation with small ceramic output capacitors that have low ESR and ESL thus are comfortably able to meet tight output voltage ripple specifications XSR or X7R dialectrics are recommended with a voltage rating of 6 3 V or 10 V Y5V and Z5U dialectrics are not recommended due to their poor temperature and dc bias characteristics Table 9 shows a list of recommended MLCC capacitors from Murata and Taiyo Yuden ee www dzsc When choosing output capacitors it is also important
11. 4 www dzsc ADP2105 ADP2106 ADP2107 NOTES 2006 2007 Analog Devices Inc All rights reserved Trademarks and ANALOG registered trademarks are the property of their respective owners 06079 0 3 07 DEVICES www analog com ps c Rev Page 32 of 32 www dzsc 6o
12. For the low fixed voltage options 1 2 V and 1 5 V poor routing of the OUT_SENSE trace can lead to noise pickup adversely affecting load regulation This can be fixed by placing a 1 nF bypass capacitor close to the OUT_SENSE pin The placement and routing of the compensation components are critical for proper behavior of the ADP2105 ADP2106 ADP2107 The compensation components should be placed as close to the COMP pin as possible It is advisable to use 0402 sized compensation components for closer placement leading to smaller parasitics Surround the compensation components with analog ground plane to prevent noise pickup Also ensure that the metal layer under the compensation components is the analog ground plane ADP2105 ADP2106 ADP2107 EVALUATION BOARD EVALUATION BOARD SCHEMATIC ADP2107 1 8V C6 c5 1MURATA X5R 0805 68 1nF 10uF GRM21BR61A106KE19L 3 22uF GRM21BR60J226ME39L g NC NO CONNECT 22uH INDUCTOR D62LCB TOKO 8 Figure 53 Evaluation Board Schematic of the ADP2107 1 8 Bold Traces High Current Paths RECOMMENDED PCB BOARD LAYOUT EVALUATION BOARD LAYOUT JUMPER TO ENABLE OUTPUT CAPACITOR INDUCTOR L 06079 045 Figure 54 Recommended Layout of Top Layer of ADP2105 ADP2106 ADP2107 Rev A Page 27 of 32 ADP2105 ADP2106 ADP2107 FEEDBACK TRACE THIS TRACE CONNECTS THE TOP OF THE RESISTIVE VOLTAGE DIVIDER ON THE FB PIN TO THE OUTPUT PLACE THIS TRACE AS FAR AWAY FROM THE
13. R BOT I STRING Rrop our FB Calculate the minimum inductor value as follows For the ADP2106 gt 0 83 uH V x Vour L gt 0 83 uH V x2 V gt L gt 1 66 uH i 4 www dzsc Rev A Page 23 of 32 Next calculate the ideal inductor value that sets the inductor peak to peak current ripple to 1 3 of the maximum load current at the maximum input voltage 2 5 Vour x V B Vin XI H Linear LOAD MAX 2 5x2x 4 2 2 42 12 The closest standard inductor value is 2 2 uH The maximum rms current of the inductor should be greater than 1 2 A and the saturation current of the inductor should be greater than 2 A One inductor that meets these criteria is the LPS4012 2 2 uH from Coilcraft Choose the output capacitor based on the transient response requirements The worst case load transient is 1 2 A for which the overshoot must be less than 100 mV which is 596 of the output voltage Therefore for a 1 A load transient the overshoot must be less than 496 of the output voltage For these conditions Figure 39 gives Output Capacitor x Output Voltage 60 uC Output Capacitor SOC 30 uF gt Output Capaci 30u Next taking into account the loss of capacitance due to bias as shown in Figure 40 two 22 uF X5R MLCC capacitors from Murata GRM21BR60J226M are sufficient for this application Because the ADP2106 is being used in this application th
14. The ADP2105 ADP2106 ADP2107 are step down dc to dc converters that use a fixed frequency peak current mode architecture with an integrated high side switch and low side synchronous rectifier The high 1 2 MHz switching frequency and tiny 16 lead 4 mm x 4 mm LFCSP_VQ package allow for a small step down dc to dc converter solution The integrated high side switch P channel MOSFET and synchronous rectifier N channel MOSFET yield high efficiency at medium to heavy loads Light load efficiency is improved by smoothly transitioning to variable frequency PFM mode The ADP2105 ADP2106 ADP2107 AD J operate with an input voltage from 2 7 V to 5 5 V and regulate an output voltage down to 0 8 V The ADP2105 ADP2106 ADP2107 are also available with preset output voltage options of 3 3 V 1 8 V 1 5 V and 1 2 V CONTROL SCHEME The ADP2105 ADP2106 ADP2107 operate with a fixed frequency peak current mode PWM control architecture at medium to high loads for high efficiency but shift to a variable frequency PFM control scheme at light loads for lower quies cent current When operating in fixed frequency PWM mode the duty cycle of the integrated switches is adjusted to regulate the output voltage but when operating in PFM mode at light loads the switching frequency is adjusted to regulate the output voltage The ADP2105 ADP2106 ADP2107 operate in the PWM mode only when the load current is greater than the pulse skipping threshold current At load
15. eese tente 31 Ordering Guide sss 31 Rev A Page 2 of 32 SPECIFICATIONS ADP2105 ADP2106 ADP2107 Vin 3 6 V Ta 25 C unless otherwise noted Bold values indicate 40 C lt T lt 125 C Table 1 Parameter Conditions Min Typ Max Unit INPUT CHARACTERISTICS Input Voltage Range 2 7 5 5 V Undervoltage Lockout Threshold Vin rising 2 2 2 4 2 6 V Vin falling 2 0 22 2 5 V Undervoltage Lockout Hysteresis 200 mV OUTPUT CHARACTERISTICS Output Regulation Voltage ADP210x 3 3 load 10 mA 3 267 33 3 333 V ADP210x 3 3 V 3 6 V to 5 5 V no load to full load 3 201 33 3 399 V ADP210x 1 8 load 10 mA 1 782 18 1 818 V ADP210x 1 8 Vin 2 7 V to 5 5 V no load to full load 1 746 18 1 854 V ADP210x 1 5 load 10 mA 1 485 1 5 1 515 V ADP210x 1 5 Vin 2 7 V to 5 5 V no load to full load 1 455 1 5 1 545 V ADP210x 1 2 load 10 mA 1 188 12 1 212 V ADP210x 1 2 Vin 2 7 V to 5 5 V no load to full load 1 164 12 1 236 V Load Regulation ADP2105 0 4 ADP2106 0 5 A ADP2107 0 6 Line Regulation ADP2105 measured in servo loop 0 1 0 33 V ADP2106 and ADP2107 measured in servo loop 0 1 0 3 Output Voltage Range ADP210x ADJ 0 8 Vin V FEEDBACK CHARACTERISTICS OUT SENSE Bias Current ADP210x 1 2 3 6 ADP210x 1 5 4 8 ADP210x 1 8 5 10 uA ADP210x 3 3 10 20 FB Regulation Voltage ADP210x ADJ 0 784 08 0 816 V FB Bias Current ADP210x AD
16. 8 V Load 0 A to 1 A 06079 049 Rev A Page 29 of 32 ADP2105 ADP2106 ADP2107 0 1 100 INPUT VOLTAGE 27V TO 4 2V OUT SENSE GND IN PWIN1 2 4pH Vour OUTPUT VOLTAGE 1 2V LOAD 0A TO 1A 1MURATA X5R 0805 4 7uF GRM21BR61A475KA73L 22uF GRM21BR60J226ME39L 2TOKO 1069AS DB3018HCT OR TOKO 1070AS DB3020HCT J NOTES 1 NC NO CONNECT 2 EXTERNAL COMPONENTS WERE CHOSEN FOR A 10 OVERSHOOT FOR A 1A LOAD TRANSIENT Figure 59 Application Circuit Vin Li lon Battery 1 2 V Load 0A to 1A 06079 050 0 1HF 409 INPUT VOLTAGE 5V OUTPUT VOLTAGE 2 5V LOAD 0A TO 1 5A 1 MURATA X5R 0805 4 GRM21BR61A475KA73L 10uF GRM21BR61A106KE19L 22uF GRM21BR60J226ME39L 2COILTRONICS 5014 2 5yH NOTES 1 NC NO CONNECT 2 EXTERNAL COMPONENTS WERE CHOSEN FOR A 5 OVERSHOOT FOR A 1A LOAD TRANSIENT Figure 60 Application Circuit Vin 5 V 2 5 V Load 0A to 1 5 A 06079 051 Rev A Page 30 of 32 ADP2105 ADP2106 ADP2107 OUTLINE DIMENSIONS p 0 60 MAX TT VIEW PIN 1 INDICATOR PIN 1 INDICATOR gt 195 5 35 SEATING 0 30 PLANE 021207 A COMPLIANT TO JEDEC STANDARDS MO 220 VGGC Figure 61 16 Lead Lead Frame Chip Scale Package LFCSP_VQ 4mm x 4 mm Body Very Thin Quad CP 16 4 Dimensions shown in millimeters ORDERING GUIDE mem Rage _ Pdage
17. LX NODE AND HIGH CURRENT TRACES AS POSSIBLE TO PREVENT NOISE PICKUP Figure 55 Recommended Layout of Bottom Layer of ADP2105 ADP2106 ADP2107 06079 046 Rev A Page 28 of 32 ADP2105 ADP2106 ADP2107 APPLICATION CIRCUITS 0 1pF 100 INPUT VOLTAGE 5V 2 5uH2 Vour OUTPUT VOLTAGE 3 3V 1MURATA X5R 0805 10 GRM21BR61A106KE19L 4 7uF GRM21BR61A475KA73L 2SUMIDA CDRH5D28 2 5uH NOTES 1 NC NO CONNECT 2 EXTERNAL COMPONENTS WERE CHOSEN FOR A 10 OVERSHOOT FOR A 1A LOAD TRANSIENT Figure 56 Application Circuit Vin 5 V Vour 3 3 V Load 0A to 2A 06079 047 0 1HF INPUT VOLTAGE 3 6V OUT_SENSE GND PWIN1 1 5 2 Vour OUTPUT VOLTAGE 1 5V LOAD 0A TO 2A 1MURATA X5R 0805 10 GRM21BR61A106KE19L 22uF GRM21BR60J226ME39L 2 D62LCB OR COILCRAFT LPS4012 NOTES 1 NC NO CONNECT 2 EXTERNAL COMPONENTS WERE CHOSEN FOR A 5 OVERSHOOT FOR A 1A LOAD TRANSIENT Figure 57 Application Circuit Vin 3 6 V Vour 1 5 V Load 0A to 2A 06079 048 40 INPUT VOLTAGE 2 7V TO 4 2V 2 7uH Vour OUTPUT VOLTAGE 1 8V LOAD 0A TO 1A 1MURATA X5R 0805 4 7uF GRM21BR61A475KA73L 22uF GRM21BR60J226ME39L 2 1098AS DE2812 2 7 5 1 NC NO CONNECT 2 EXTERNAL COMPONENTS WERE CHOSEN FOR A 5 OVERSHOOT FOR A 1A LOAD TRANSIENT Figure 58 Application Circuit Vin Li lon Battery 1
18. can be approxi mated by Psw Rpstow p X D Roson n x 1 D x Iovr where D Vovr Vm The internal resistance of the power switches increases with temperature but decreases with higher input voltage Figure 19 and Figure 20 show the change in RDS ON vs input voltage whereas Figure 28 and Figure 29 show the change in Roson vs temperature for both power devices Inductor Losses Inductor conduction losses are caused by the flow of current through the inductor which has an internal resistance DCR associated with it Larger sized inductors have smaller DCR which can improve inductor conduction losses Inductor core losses are related to the magnetic permeability of the core material Because the ADP2105 ADP2106 ADP2107 are high switching frequency dc to dc converters shielded ferrite core material is recommended for its low core losses and low EMI The total amount of inductor power loss can be calculated by DCR x Core Losses Switching Losses Switching losses are associated with the current drawn by the driver to turn on and turn off the power devices at the switching frequency Each time a power device gate is turned on and turned off the driver transfers a charge AQ from the input supply to the gate and then from the gate to ground The amount of power loss can by calculated by Psw Coare P Coare x Vin X fsw where Coare Ceare n 600 pF oo wWwW dz
19. connect PGND to the exposed pad of the ADP2105 ADP2106 ADP2107 ADP2105 ADP2106 ADP2107 Power Input The power source for the ADP2105 ADP2106 ADP2107 internal circuitry Connect IN and PWIN1 with a 10 resistor as close as possible to the ADP2105 ADP2106 ADP2107 Bypass IN to AGND with a 0 1 or greater capacitor See the Input Filter section Output Voltage Sense or Feedback Input For fixed output versions connect OUT SENSE to the output voltage For adjustable versions FB is the input to the error amplifier Drive FB through a resistive voltage divider to set the output voltage The FB regulation voltage is 0 8 V www dzsc HOA Rev A Page 6 of 32 ADP2105 ADP2106 ADP2107 TYPICAL PERFORMANCE CHARACTERISTICS 100 95 Vin 3 6 90 Vin 2 7V S 85 gt gt gt 9 bo 5 80 7 2 o 2 e Vin 4 2 ira 75 E Vin 5 5V IN 65 INDUCTOR 5014 2 5 3 INDUCTOR 503814 3 3yH DCR 60mQ DCR 93
20. currents below this value the converter smoothly transitions to the PFM mode of operation PWM MODE OPERATION In PWM mode the ADP2105 ADP2106 ADP2107 operate at a fixed frequency of 1 2 MHz set by an internal oscillator At the start of each oscillator cycle the P channel MOSFET switch is turned on putting a positive voltage across the inductor Current in the inductor increases until the current sense signal crosses the peak inductor current level that turns off the P channel MOSFET switch and turns on the N channel MOSFET synchro nous rectifier This puts a negative voltage across the inductor causing the inductor current to decrease The synchronous rectifier stays on for the rest of the cycle unless the inductor current reaches zero which causes the zero crossing comparator to turn off the N channel MOSFET as well The peak inductor current is set by the voltage on the COMP pin The COMP pin is the output of a transconductance error amplifier that compares the feedback voltage with an internal 0 8 V reference 0 amp www dzsc PFM MODE OPERATION The ADP2105 ADP2106 ADP2107 smoothly transition to the variable frequency mode of operation when the load current decreases below the pulse skipping threshold current switching only as necessary to maintain the output voltage within regulation When the output voltage dips below regulation the ADP2105 ADP2106 ADP2107 enter PWM mode for a few oscillator cycles t
21. mO x 0 5 90 mO x 0 5 x 2 A 400 mW The for the LFCSP_VQ package is 40 C W as shown in Table 3 Thus the rise in temperature of the package due to power dissipation is Tr x Pp 40 C W x 0 40 W 16 The junction temperature of the converter is Ta Tr 85 16 101 C which is below the maximum junction temperature of 125 C Thus this application operates reliably from a thermal point of view DESIGN EXAMPLE Consider an application with the following specifications Input Voltage 3 6 V to 4 2 V Output Voltage 2 V Typical Output Current 600 mA Maximum Output Current 1 2 A Soft Start Time 2 ms Overshoot lt 100 mV under all load transient conditions 1 Choose the dc to dc converter that satisfies the maximum 5 output current requirement Because the maximum output current for this application is 1 2 A the ADP2106 with a maximum output current of 1 5 A is ideal for this 6 application 2 whether the output voltage desired is available as a fixed output voltage option Because 2 V is not one of the 7 fixed output voltage options available choose the adjustable version of ADP2106 3 The first step in external component selection for an adjustable version converter is to calculate the resistance of the resistive voltage divider that sets the output voltage Vs 08V 20 uA V 2V 0 8V F 40 kQ x 60 0 8 V
22. oscil lator remains off until the inductor current reaches the peak inductor current level at which time the switch is turned off and the synchronous rectifier is turned on for a fixed off time At the end of the fixed off time another cycle is initiated As the ADP2105 ADP2106 ADP2107 approach dropout the switching frequency decreases gradually to smoothly transition to 100 duty cycle operation Rev A Page 13 of 32 ADP2105 ADP2106 ADP2107 SLOPE COMPENSATION Slope compensation stabilizes the internal current control loop of the ADP2105 ADP2106 ADP2107 when operating beyond 50 duty cycle to prevent subharmonic oscillations It is imple mented by summing a fixed scaled voltage ramp to the current sense signal during the on time of the P channel MOSFET switch The slope compensation ramp value determines the minimum inductor that can be used to prevent subharmonic oscillations at a given output voltage The slope compensation ramp values for ADP2105 ADP2106 ADP2107 follow For more information see the Inductor Selection section For the ADP2105 Slope Compensation Ramp Value 0 72 A us For the ADP2106 Slope Compensation Ramp Value 1 07 A us For the ADP2107 Slope Compensation Ramp Value 1 38 A us FEATURES Enable Shutdown Drive EN high to turn on the ADP2105 ADP2106 ADP2107 Drive EN low to turn off the ADP2105 ADP2106 ADP2107 reducing input current below 0 1 pA To force the ADP2105 ADP2106 ADP2107 to auto
23. the soft start period connect a soft start capacitor Css from SS to AGND The soft start period varies linearly with the size of the soft start capacitor as shown in the following equation Tss Css x 10 ms To get a soft start period of 1 ms a 1 nF capacitor must be connected between SS and AGND LOOP COMPENSATION The ADP2105 ADP2106 ADP2107 utilize a transconductance error amplifier to compensate the external voltage loop The open loop transfer function at angular frequency s is given by He c c Zane OUT OUT where Vrer is the internal reference voltage 0 8 V Vovr is the nominal output voltage Zcour s is the impedance of the compensation network at the angular frequency s Covr is the output capacitor Gn is the transconductance of the error amplifier 50 A V nominal Gcs is the effective transconductance of the current loop Gcs 1 875 A V for the ADP2105 Gcs 2 8125 A V for the ADP2106 Gcs 3 625 A V for the ADP2107 i 4 www dzsc The transconductance error amplifier drives the compensation network that consists of a resistor Rcome and capacitor Ccomp connected in series to form a pole and a zero as shown in the following equation 1 1 sR Zcomp Ss Rew SRcompCcomp 5 SCcomp At the crossover frequency the gain of the open loop transfer function is unity This yields the following equation for the compensation network impedance at th
24. vs Input Voltage ADP2106 and ADP2107 1 75 1260 1 70 1250 1240 ADP2105 1A 1230 1220 1210 PEAK CURRENT LIMIT A m o SWITCHING FREQUENCY kHz 1200 1 30 5 8 Ta 25 5 5 1 25 1190 8 27 30 33 36 39 42 45 48 51 54 57 27 30 33 36 39 42 45 48 51 54 INPUT VOLTAGE INPUT VOLTAGE V Figure 18 Peak Current Limit of ADP2105 Figure 21 Switching Frequency vs Input Voltage Rev A Page 9 of 32 www dzsc ADP2105 ADP2106 ADP2107 2 35 HH 2 25 2 20 ADP2106 1 5 2 15 2 10 2 05 2 00 CURRENT LIMIT 1 95 1 90 06079 072 1 85 27 30 33 36 39 42 45 48 51 54 57 INPUT VOLTAGE V Figure 22 Peak Current Limit of ADP2106 Ine 3 00 2 95 2 90 2 85 2 80 2 75 2 70 2 65 PEAK CURRENT LIMIT A 2 60 2 55 06079 071 AD 25 C 27 30 33 36 39 42 45 48 51 54 57 INPUT VOLTAGE V Figure 23 Peak Current Limit of ADP2107 2 50 150 135 120 105 PULSE SKIPPING THRESHOLD CURRENT mA A a 06079 067 8 51 54 57 INPUT VOLTAGE V Figure 24 Pulse Skipping Threshold vs Input Voltage for ADP2106 Rev A Page 10 of 32 LX NODE SWITCH NODE INDUCTOR CURRENT T
25. 0 OUTPUT CAPACITOR 22 22uF 4 7 OUTPUT CAPACITOR 22yF 4 7uF INDUCTOR 5014 2 5 COMPENSATION RESISTOR 270kQ COMPENSATION RESISTOR 135kQ COMPENSATION CAPACITOR 39pF COMPENSATION CAPACITOR 82pF Figure 47 1 A Load Transient Response for ADP2105 1 2 Figure 50 1 A Load Transient Response for ADP2105 1 2 with External Components Chosen for 5 Overshoot with External Chosen for 10 Overshoot INDUCTOR SD14 2 5pH 06079 087 06079 090 OUTPUT CURRENT OUTPUT VOLTAGE AC COUPLED T LX NODE SWITCH NODE CH1 2 00V 100mV M20 0us 700mA CH1 2 00V 100 M20 0us 700mA CH3 1 00A Q 10 00 CH3 1 00A 10 00 OUTPUT CAPACITOR 22uF 22uF OUTPUT CAPACITOR 10pF 10pF INDUCTOR 503814 3 COMPENSATION RESISTOR 270 COMPENSATION CAPACITOR 39pF Figure 48 1 A Load Transient Response for ADP2105 1 8 Figure 51 1 A Load Transient Response for ADP2105 1 8 with External Components Chosen for 5 Overshoot with External Components Chosen for 10 Overshoot INDUCTOR SD3814 3 3HH COMPENSATION RESISTOR 135kO COMPENSATION CAPACITOR 82pF 06079 088 06079 091 OUTPUT VOLTAGE AC COUPLED LX NODE SWITCH NODE LX NODE SWITCH NODE 2 00V HH 200 M20 0us A 700 200V H 200mV M20 0ps A
26. 10 10 10 2 2 90 100 50 40 ADP2106 ADJ 2 5 4 7 10 104 4 7 2 5 90 100 85 40 ADP2106 ADJ 3 3 4 7 10 104 4 7 3 0 90 100 125 40 ADP2107 ADJ 0 9 10 10 22 10 1 2 70 120 5 40 ADP2107 ADJ 1 2 10 10 2244 1 5 70 120 20 40 ADP2107 ADJ 1 5 10 10 104 10 1 5 70 120 35 40 ADP2107 ADJ 1 8 10 10 10 10 1 8 70 120 50 40 ADP2107 ADJ 2 5 10 10 104 4 7 1 8 70 120 85 40 ADP2107 ADJ 3 3 10 10 104 4 7 2 5 70 120 125 40 ADP2105 1 2 1 2 4 7 47 22 47 2 5 135 82 ADP2105 1 5 1 5 4 7 4 7 104 10 3 0 135 82 ADP2105 1 8 1 8 4 7 4 7 104 10 3 3 135 82 ADP2105 3 3 3 3 4 7 4 7 104 4 7 4 1 135 82 ADP2106 1 2 1 2 4 7 10 2244 1 8 90 100 ADP2106 1 5 1 5 4 7 10 10 10 2 0 90 100 ADP2106 1 8 1 8 4 7 10 104 10 2 2 90 100 ADP2106 3 3 3 3 4 7 10 104 4 7 3 0 90 100 ADP2107 1 2 1 2 10 10 22 47 1 5 70 120 ADP2107 1 5 1 5 10 10 10 10 1 5 70 120 ADP2107 1 8 1 8 10 10 10 10 1 8 70 120 ADP2107 3 3 3 3 10 10 104 4 7 2 5 70 120 14 7 uF 0805 X5R 10 V Murata GRM21BR61A475KA73L 10 uF 0805 X5R 10 V Murata GRM21BR61A106KE19L 24 7 uF 0805 X5R 10 V Murata GRM21BR61A475KA73L 10 uF 0805 X5R 10 V Murata GRM21BR61A106KE19L 34 7 uF 0805 X5R 10 V Murata GRM21BR61A475KA73L 10 uF 0805 X5R 10 V Murata GRM21BR614A106KE19L 22 uF 0805 X5R 6 3 V Murata GRM21BR60J226ME39L 40 5 accuracy resistor 5 0 596 accuracy resistor Rev A Page 24 of 32 OD 1g www dzsc ADP2105 ADP2106 ADP2107 Table 11
27. 106 1 8 1 8 4 7 10 22 22 22 180 56 ADP2106 3 3 3 3 4 7 10 22 4 7 3 0 180 56 ADP2107 1 2 1 2 10 10 22 22 47 1 5 140 68 ADP2107 1 5 1 5 10 10 22 22 1 5 140 68 ADP2107 1 8 1 8 10 10 22 22 1 8 140 68 ADP2107 3 3 3 3 10 10 22 4 7 2 5 140 68 14 7 0805 X5R 10V Murata GRM21BR61A475KA73L 0805 X5R 10V Murata GRM21BR61A106KE19L 4 7 0805 X5R 10V Murata GRM21BR61A475KA73L 10pF 0805 X5R 10V Murata GRM21BR61A106KE19L 3 4 7uF 0805 X5R 10V Murata GRM21BR61A475KA73L 0805 X5R 10V Murata GRM21BR61A106KE19L 22uF 0805 X5R 6 3V Murata GRM21BR60J226ME39L 0 596 accuracy resistor 5 0 596 accuracy resistor a Rev A Page 25 of 32 HE www dzsc ADP2105 ADP2106 ADP2107 CIRCUIT BOARD LAYOUT RECOMMENDATIONS Good circuit board layout is essential to obtaining the best performance from the ADP2105 ADP2106 ADP2107 Poor circuit layout degrades the output ripple as well as the electromagnetic interference EMI and electromagnetic compatibility EMC performance Figure 54 and Figure 55 show the ideal circuit board layout for the ADP2105 ADP2106 ADP2107 Use this layout to achieve the highest performance Refer to the following guidelines if adjustments to the suggested layout are needed e Use separate analog and power ground planes Connect the ground reference of sensitive analog circuitry such as compensation and output voltage divider components to analog ground connect the gro
28. Exposure to absolute maximum rating conditions for extended periods may affect device reliability Vx 1g E www dzsc Package Type Osa Unit 16 Lead LFCSP_VQ QFN 40 C W Maximum Power Dissipation 1 BOUNDARY CONDITION Natural convection 4 layer board exposed pad soldered to the PCB ESD CAUTION ESD electrostatic discharge sensitive device Charged devices and circuit boards can discharge without detection Although this product features patented or proprietary protection circuitry damage may occur on devices subjected to high energy ESD Therefore proper ESD precautions should be taken to avoid performance degradation or loss of functionality Rev A Page 5 of 32 ADP2105 ADP2106 ADP2107 PIN CONFIGURATION AND FUNCTION DESCRIPTIONS Table 4 Pin Function Descriptions m o z n LT PIN 1 A INDICATOR 13 PWIN1 ADP2105 ADP2106 ADP2107 TOP VIEW Not to Scale CI 2 NC NO CONNECT 06079 003 Figure 3 Pin Configuration Mnemonic ADP210x xx ADP210x ADJ Description 11 14 16 EN GND COMP SS AGND NC PWIN2 PWIN1 LX1 LX2 PGND OUT_SENSE EN GND COMP SS AGND NC PWIN2 PWIN1 LX1 LX2 PGND FB Enable Input Drive EN high to turn on the ADP2105 ADP2106 ADP2107 Drive EN low to turn it off and reduce the input current to 0 1 PA Test Pins Th
29. INPUT VOLTAGE 5V LOAD CURRENT 1A FREQUENCY 76kHz 135 180 INDUCTOR 24H D62LCB OUTPUT CAPACITOR 10pF 4 7 COMPENSATION RESISTOR 70 COMPENSATION CAPACITOR 120pF 10 kHz NOTES 100 1 EXTERNAL COMPONENTS WERE CHOSEN FORA 10 OVERSHOOT FOR A 1A LOAD TRANSIENT ADP2107 LOOP GAIN 0 45 PHASE MARGIN 70 90 LOOP PHASE 135 DSL 8 e OUTPUT VOLTAGE 3 3V CROSSOVER INPUT VOLTAGE 5V FREQUENCY 67kHz LOAD CURRENT 1A INDUCTOR 2 5pH CDRH5D28 OUTPUT CAPACITOR 10pF 4 7 COMPENSATION RESISTOR 70kQ COMPENSATION CAPACITOR 120pF 10 kHz NOTES 100 300 1 EXTERNAL COMPONENTS WERE CHOSEN FORA 10 OVERSHOOT FOR A 1A LOAD TRANSIENT LOOP PHASE Degrees Figure 44 ADP2105 Bode Plot at Vin 5 5 V Vour 1 2 Vand Load 1 A LOOP PHASE Degrees Figure 45 ADP2107 Bode Plot at Vi 5 V Vour 2 5 Vand Load 1 A LOOP PHASE Degrees Figure 46 ADP2107 Bode Plot at Viv 5 V 3 3 V and Load 1 A 06079 058 06079 059 06079 069 ADP2105 ADP2106 ADP2107 LOAD TRANSIENT RESPONSE OUTPUT CURRENT OUTPUT VOLTAGE i CH1 2 00V 100mV 20 08 CH3 700mA CH1 2 00V 100mV M20 0us CH3 700mA LX NODE SWITCH NODE CH3 1 00A 10 00 CH3 1 00 Q 10 0
30. J 0 1 0 1 pA INPUT CURRENT CHARACTERISTICS IN Operating Current ADP210x ADJ Vrs 0 9 V 20 30 ADP210x xx output voltage 10 above regulation voltage 20 30 uA IN Shutdown Current 0 0 1 1 uA LX SWITCH NODE CHARACTERISTICS LX Resistance P channel switch ADP2105 190 270 P channel switch ADP2106 ADP2107 100 165 N channel synchronous rectifier ADP2105 160 230 N channel synchronous rectifier ADP2106 ADP2107 90 140 LX Leakage Current gt Vn 5 5 V V x O V 5 5 V 0 1 1 uA LX Peak Current Limit P channel switch ADP2107 2 6 2 9 3 3 A P channel switch ADP2106 2 0 2 25 2 6 A P channel switch ADP2105 1 3 1 5 1 8 A LX Minimum On Time In PWM mode of operation Vin 5 5 V 100 ns ENABLE CHARACTERISTICS EN Input High Voltage Vn 2 7 V to 5 5 V 2 EN Input Low Voltage Vin 2 7 V to 5 5 V 0 4 V EN Input Leakage Current Vin 5 5 V Ven O V 5 5 V 1 0 1 1 OSCILLATOR FREQUENCY Vin 2 7Vto5 5V 1 1 2 1 4 MHz SOFT START PERIOD Css 1 nF 750 1000 1200 us i HE www dzsc Rev A Page 3 of 32 ADP2105 ADP2106 ADP2107 Parameter Conditions Min Typ Max Unit THERMAL CHARACTERISTICS Thermal Shutdown Threshold 140 Thermal Shutdown Hysteresis 40 C COMPENSATOR TRANSCONDUCTANCE Gm 50 CURRENT SENSE AMPLIFIER GAIN Gcs ADP2105 1 875 A V ADP2106 2 8125 A V ADP2107 3 625 A V 1 All limits at temperature extremes are guaranteed
31. Recommended External Components for Popular Output Voltage Options at 80 kHz Crossover Frequency with 5 Overshoot for a 1 A Load Transient Refer to Figure 37 and Figure 38 Part Vout V Cini Cour pF L pH Rcome Ccomp pF Reor ADP2105 ADJ 0 9 4 7 4 7 22422422 2 0 270 39 5 40 ADP2105 ADJ 1 2 4 7 4 7 22 22 47 2 5 270 39 20 40 ADP2105 ADJ 1 5 4 7 4 7 22 22 3 0 270 39 35 40 ADP2105 ADJ 1 8 4 7 4 7 22 22 3 3 270 39 50 40 ADP2105 ADJ 2 5 4 7 4 7 22 10 3 6 270 39 85 40 ADP2105 ADJ 3 3 4 7 4 7 22 4 7 4 1 270 39 125 40 ADP2106 ADJ 0 9 4 7 10 22422422 1 5 180 56 5 40 ADP2106 ADJ 1 2 4 7 10 22 22 47 1 8 180 56 20 40 ADP2106 ADJ 1 5 4 7 10 22 22 2 0 180 56 35 40 ADP2106 ADJ 1 8 4 7 10 22 22 22 180 56 50 40 ADP2106 ADJ 2 5 4 7 10 22 10 2 5 180 56 85 40 ADP2106 ADJ 3 3 4 7 10 22444 3 0 180 56 125 40 ADP2107 ADJ 0 9 10 10 22422422 1 2 140 68 5 40 ADP2107 ADJ 1 2 10 10 22 22 47 1 5 140 68 20 40 ADP2107 ADJ 1 5 10 10 22 22 1 5 140 68 35 40 ADP2107 ADJ 1 8 10 10 22 22 1 8 140 68 50 40 ADP2107 ADJ 2 5 10 10 22 10 1 8 140 68 85 40 ADP2107 ADJ 3 3 10 10 22 47 2 5 140 68 125 40 ADP2105 1 2 1 2 4 7 4 7 22 22 47 2 5 270 39 ADP2105 1 5 1 5 4 7 4 7 22 22 3 0 270 39 ADP2105 1 8 1 8 4 7 4 7 22 22 3 3 270 39 ADP2105 3 3 3 3 4 7 4 7 22 47 4 1 270 39 ADP2106 1 2 1 2 4 7 10 22 22 47 1 8 180 56 ADP2106 1 5 1 5 4 7 10 22 22 2 0 180 56 ADP2
32. S to rise linearly The output voltage rises linearly with the voltage at SS Rev A Page 14 of 32 ADP2105 ADP2106 ADP2107 REFERENCE 0 8V CURRENT SENSE AMPLIFIER CURRENT PWM LIMIT CONTROL FOR PRESET VOLTAGES OPTIONS ONLY DRIVER AND ANTI SHOOT THROUGH SLOPE COMPENSATION OSCILLATOR ZERO CROSS COMPARATOR THERMAL SHUTDOWN 06079 037 1FB FOR ADP210x ADJ ADJUSTABLE VERSION AND OUT_SENSE FOR ADP210x xx FIXED VERSION Figure 36 Block Diagram of the ADP2105 ADP2106 ADP2107 Rev A Page 15 of 32 www dzsc ADP2105 ADP2106 ADP2107 APPLICATIONS INFORMATION EXTERNAL COMPONENT SELECTION The external component selection for the ADP2105 ADP2106 ADP2107 application circuits shown in Figure 37 and Figure 38 depend on input voltage output voltage and load current requirements Additionally trade offs between performance parameters like efficiency and transient response can be made by varying the choice of external components SETTING THE OUTPUT VOLTAGE The output voltage of ADP2105 ADP2106 ADP2107 ADJ is externally set by a resistive voltage divider from the output voltage to FB The ratio of the resistive voltage divider sets the output voltage and the absolute value of those resistors sets the divider string current For lower divider string currents the small 10 nA 0 1 uA maximum FB bias current should be taken 0 4pF 100 ADP2106 ADP2107 LX1 T NC
33. Slope Compensation 14 noil 14 Applications Information eene 16 REVISION HISTORY 3 07 Rev 0 to Rev A Updated Format siirretiin Universal Changes to Output Characteristics and LX Switch Node Characteristics Sections 3 Changes to Typical Performance Characteristics Section 7 Changes to Load Transient Response Section 21 7 06 Revision 0 Initial Version i 4 www dzsc External Component Selection sss 16 Setting the Output Voltage sse 16 Inductor Selection serene 17 Output Capacitor Selection sse 18 Input Capacitor Selection 18 Input Filter C 19 Sri 19 Loop Compensation eene 19 Pode ense heus 20 Load Transient Response isnin 21 Efficiency Considerations 22 Thermal 22 Design 2 00 External Component Recommendations Circuit Board Layout Recommendations 50 Evaluation Board eese 27 Evaluation Board Schematic ADP2107 1 8V 27 Recommended PCB Board Layout Evaluation Board Layout 27 Application Circuits essent 29 Outline Dimensions
34. T 1 260mv i OUTPUT VOLTAGE 4 1V M 10ps A CH1 1 78V CH3 5V CH4 1 45 8 Figure 25 Short Circuit Response at Output 135 120 105 Vour 1 2V 45 Vour 1 8V Vout 2 5V PULSE SKIPPING THRESHOLD CURRENT mA 06079 066 25 C 27 30 33 36 39 42 45 48 51 54 57 INPUT VOLTAGE Figure 26 Pulse Skipping Threshold vs Input Voltage for ADP2105 195 180 165 Vout 1 2V 150 135 120 105 90 75 60 45 Vour 1 8V Vout 2 5 PULSE SKIPPING THRESHOLD CURRENT mA 06079 068 Ta 25 C 27 30 33 36 39 42 45 48 51 54 57 INPUT VOLTAGE V Figure 27 Pulse Skipping Threshold vs Input Voltage for ADP2107 9 PMOS POWER SWITCH 2 7 2 5 NMOS SYNCHRONOUS RECTIFIER E z o 40 20 0 20 40 60 80 100 120 JUNCTION TEMPERATURE C Figure 28 Switch On Resistance vs Temperature ADP2105 PMOS POWER SWITCH z N u NOUS RECTIFIER z 5 o 20 40 60 80 100 120 JUNCTION TEMPERATURE Figure 29 Switch On Resistance vs Temperature ADP2106 and ADP2107 LX NODE SWITCH NODE l INDUCTOR CURRENT 50mV M 2ps CH3 2V CH4 200
35. Undervoltage Lockout UVLO To protect against deep battery discharge undervoltage lockout circuitry is integrated on the ADP2105 ADP2106 ADP2107 If the input voltage drops below the 2 2 V UVLO threshold the ADP2105 ADP2106 ADP2107 shutdown and both the power switch and synchronous rectifier turn off Once the voltage rises again above the UVLO threshold the soft start period is initiated and the part is enabled Thermal Protection In the event that the ADP2105 ADP2106 ADP2107 junction temperatures rise above 140 C the thermal shutdown circuit turns off the converter Extreme junction temperatures can be the result of high current operation poor circuit board design and or high ambient temperature A 40 C hysteresis is included so that when thermal shutdown occurs the ADP2105 ADP2106 ADP2107 do not return to operation until the on chip tempera ture drops below 100 C When coming out of thermal shutdown soft start is initiated Soft Start The ADP2105 ADP2106 ADP2107 include soft start circuitry to limit the output voltage rise time to reduce inrush current at startup To set the soft start period connect the soft start capacitor Css from SS to AGND When the ADP2105 ADP2106 ADP2107 are disabled or if the input voltage is below the under voltage lockout threshold Css is internally discharged When the ADP2105 ADP2106 ADP2107 are enabled Css is charged through an internal 0 8 uA current source causing the voltage at S
36. e input capacitors are 10 uF and 4 7 uF X5R Murata capacitors GRM21BR61A106K and GRM21BR61A475K The input filter consists of a small 0 1 uF ceramic capacitor placed between IN and AGND and a 10 resistor placed between IN and PWINI Choose a soft start capacitor of 2 nF to achieve a soft start time of 2 ms Finally the compensation resistor and capacitor can be calculated as 271 Feross_ Cour Your REF Rcomp osf 1 21 x 80 kHz uFx2 V 215 50 uA V x2 8125 A V 0 8 V 2 2 TX 80 kHz x215 39 pF ADP2105 ADP2106 ADP2107 EXTERNAL COMPONENT RECOMMENDATIONS Table 10 Recommended External Components for Popular Output Voltage Options at 80 kHz Crossover Frequency with 10 Overshoot for a 1 A Load Transient Refer to Figure 37 and Figure 38 Part Cini pF pF Cour pF L uH pF ADP2105 ADJ 0 9 4 7 4 7 224 10 2 0 135 82 5 40 ADP2105 ADJ 1 2 4 7 4 7 2244 2 5 135 82 20 40 ADP2105 ADJ 1 5 4 7 4 7 104 10 3 0 135 82 35 40 ADP2105 ADJ 1 8 4 7 4 7 104 10 3 3 135 82 50 40 ADP2105 ADJ 2 5 4 7 4 7 104 4 7 3 6 135 82 85 40 ADP2105 ADJ 33 4 7 4 7 104 4 7 4 1 135 82 125 40 ADP2106 ADJ 0 9 4 7 10 22 10 1 5 90 100 5 40 ADP2106 ADJ 1 2 4 7 10 22444 1 8 90 100 20 40 ADP2106 ADJ 1 5 4 7 10 10 10 2 0 90 100 35 40 ADP2106 ADJ 1 8 4 7
37. e crossover frequency 27 Feross CourVour G Ges V REF ZcourFcnoss where Fcross 80 kHz the crossover frequency of the loop CourVour is determined from the Output Capacitor Selection section To ensure that there is sufficient phase margin at the crossover frequency place the Compensator Zero at 1 4 of the crossover frequency as shown in the following equation aes 1 Solving the three equations above simultaneously yields the value for the compensation resistor and compensation capacitor as shown in the following equation Rcomp 0 8 27 Foross G Ges Veer 2 TE cross Rcomp Rev A Page 19 of 32 ADP2105 ADP2106 ADP2107 BODE PLOTS 60 50 40 30 20 LOOP GAIN dB Figure 41 ADP2106 Bode Plot at Vw 5 5 V Vour 1 8 Vand Load 1 A LOOP GAIN dB Figure 42 ADP2106 Bode Plot at Vin 3 6 V Vour 1 8 V andLoad 1A LOOP GAIN dB Figure 43 ADP2105 Bode Plot at Vin 3 6 V Vout 1 2 V and Load 1 A ADP2106 OUTPUT VOLTAGE 1 8V INPUT VOLTAGE 5 5 FREQUENCY LOAD CURRENT 1A INDUCTOR 2 2 LPS4012 OUTPUT CAPACITOR 22uF 22uF COMPENSATION RESISTOR 180kO COMPENSATION CAPACITOR 56pF 1 10 kHz NOTES 100 300 1 EXTERNAL COMPONENTS WERE CHOSEN FORA 5 OVERSHOOT FOR A 1A LOAD TRANSIENT
38. e temperature rise of the package due to the power dissipation as shown in the following equation Tr where is the junction temperature is the ambient temperature Tr is the rise in temperature of the package due to power dissipation in it The rise in temperature of the package is directly proportional to the power dissipation in the package The proportionality constant for this relationship is defined as the thermal resistance from the junction of the die to the ambient temperature as shown in the following equation Tr 0j x Pp where Tr is the rise in temperature of the package Ppis the power dissipation in the package is the thermal resistance from the junction of the die to the ambient temperature of the package For example consider an application where the ADP2107 1 8 is used with an input voltage of 3 6 V and a load current of 2 A Also assume that the maximum ambient temperature is 85 C Rev A Page 22 of 32 ADP2105 ADP2106 ADP2107 At a load current of 2 A the most significant contributor of power dissipation in the dc to dc converter package is the conduction loss of the power switches Using the graph of switch resistance vs temperature see Figure 29 as well as the equation of power loss given in the Power Switch Conduction Losses section the power dissipation in the package can be calculated by Psw p X D Roson n X 1 D x Iovi 109
39. ed that each PWIN pin be bypassed with a 4 7 uF or larger input capacitor For the ADP2106 bypass the PWIN pins with a 10 and a 4 7 uF capacitor and for the ADP2107 bypass each PWIN pin with a 10 capacitor As with the output capacitor a low ESR ceramic capacitor is recommended to minimize input voltage ripple XSR or X7R dialectrics are recommended with a voltage rating of 6 3 V or 10 V Y5V and Z5U dialectrics are not recommended due to their poor temperature and dc bias characteristics Refer to Table 9 for input capacitor recommendations Rev A Page 18 of 32 ADP2105 ADP2106 ADP2107 INPUT FILTER The IN pin is the power source for the ADP2105 ADP2106 ADP2107 internal circuitry including the voltage reference and current sense amplifier that are sensitive to power supply noise To prevent high frequency switching noise on the PWIN pins from corrupting the internal circuitry of the ADP2105 ADP2106 ADP2107 a low pass RC filter should be placed between the IN pin and the PWINI pin The suggested input filter consists of a small 0 1 uF ceramic capacitor placed between IN and AGND and a 10 resistor placed between IN and PWIN1 This forms a 150 kHz low pass filter between PWINI and IN that prevents any high frequency noise on PWINI from coupling into the IN pin SOFT START The ADP2105 ADP2106 ADP2107 include soft start circuitry to limit the output voltage rise time to reduce inrush current at startup To set
40. ernal circuitry required Connect the OUT_SENSE to the output voltage as close as possible to the load for improved load regulation INDUCTOR SELECTION The high switching frequency of ADP2105 ADP2106 ADP2107 allows for minimal output voltage ripple even with small inductors The sizing of the inductor is a trade off between efficiency and transient response A small inductor leads to larger inductor current ripple that provides excellent transient response but degrades efficiency Due to the high switching frequency of ADP2105 ADP2106 ADP2107 shielded ferrite core inductors are recommended for their low core losses and low EMI As a guideline the inductor peak to peak current ripple is typically set to 1 3 of the maximum load current for optimal transient response and efficiency AL Vour 7 IioAD MAX t Vin X XL 3 L prar 2 5x Vour X Viy Vour uH Vin 1 where fsw is the switching frequency 1 2 MHz The ADP2105 ADP2106 ADP2107 use slope compensation in the current control loop to prevent subharmonic oscillations when operating beyond 5096 duty cycle The fixed slope compen sation limits the minimum inductor value as a function of output voltage For the ADP2105 L gt 1 12 H V x Vour For the ADP2106 gt 0 83 uH V x Vour For the ADP2107 L gt 0 66 uH V x Vovr Also 4 7 uH or larger inductors are not recommended because they may cause instability in discontinu
41. ese pins are used by Analog Devices Inc for internal testing and are not ground return pins Tie these pins to the AGND plane as close to the ADP2105 ADP2106 ADP2107 as possible Feedback Loop Compensation Node COMP is the output of the internal transconductance error amplifier Place a series RC network from COMP to AGND to compensate the converter See the Loop Compensation section Soft Start Input Place a capacitor from SS to AGND to set the soft start period A 1 nF capacitor sets a 1 ms soft start period Analog Ground Connect the ground of the compensation components soft start capacitor and the voltage divider on the FB pin to the AGND pin as close as possible to the ADP2105 ADP2106 ADP2107 Also connect AGND to the exposed pad of ADP2105 ADP2106 ADP2107 No Connect Not internally connected Can be connected to other pins or left unconnected Power Source Inputs The source of the PFET high side switch Bypass each PWIN pin to the nearest PGND plane with a 4 7 uF or greater capacitor as close as possible to the ADP2105 ADP2106 ADP2107 See the Input Capacitor Selection section Switch Outputs The drain of the P channel power switch and N channel synchronous rectifier Tie the two LX pins together and connect the output LC filter between LX and the output voltage Power Ground Connect the ground return of all input and output capacitors to PGND pin using a power ground plane as close as possible to the ADP2105 ADP2106 ADP2107 Also
42. mQ S TA 25 C 5 25 C 5 1 10 100 1000 1 10 100 1000 LOAD CURRENT mA LOAD CURRENT mA Figure 4 Efficiency ADP2105 1 2 V Output Figure 7 Efficiency ADP2105 1 8 V Output 100 100 95 90 F Viy 3 6V Vin 2 70 90 85 E 85 80 5 5 Vin 4 2V 80 a 75 o o 75 Vin 5 5V 65 70 60 65 INDUCTOR 5018 4 1gH INDUCTOR D62LCB 2pH DCR 43mQ 9 DCR 28mO 8 25 C 5 25 C 5 60 8 50 8 1 10 100 1000 1 10 100 1000 10000 LOAD CURRENT mA LOAD CURRENT mA Figure 5 Efficiency ADP2105 3 3 V Output Figure 8 Efficiency ADP2106 1 2 V Output 100 100 Vin 3 6V TM 95 95 77 N 90 90 Vin 2 7V 85 85 4 Vin 5 5 Vin 4 2V 2 T f 80 S 8 S Vin 4 2 LT 75 8 75 9 5 Vin 5 5V 5 i 70 70 65 65 60 60 Vin 3 6V 55 INDUCTOR D62LCB 2pH 9 INDUCTOR D62LCB 3 DCR 28 DCR 47 F 25 C S 25 C 5 50 8 50 8 1 10 100 1000 10000 1 10 100 1000 10000 LOAD CURRENT mA LOAD CURRENT mA Figure 6 Efficiency ADP2106 1 8 V Output Figure 9 Efficiency ADP2106 3 3 V Output Rev A Page 7 of 32 www dzsc ADP2105 ADP2106 ADP2107
43. matically start when input power is applied connect EN to IN When shut down the ADP2105 ADP2106 ADP2107 discharge the soft start capacitor causing a new soft start cycle every time they are re enabled Synchronous Rectification In addition to the P channel MOSFET switch the ADP2105 ADP2106 ADP2107 include an integrated N channel MOSFET synchronous rectifier The synchronous rectifier improves efficiency especially at low output voltage and reduces cost and board space by eliminating the need for an external rectifier Current Limit The ADP2105 ADP2106 ADP2107 have protection circuitry to limit the direction and amount of current flowing through the power switch and synchronous rectifier The positive current limit on the power switch limits the amount of current that can flow from the input to the output and the negative current limit on the synchronous rectifier prevents the inductor current from reversing direction and flowing out of the load 0 amp www dzsc Short Circuit Protection The ADP2105 ADP2106 ADP2107 include frequency foldback to prevent output current runaway on a hard short When the voltage at the feedback pin falls below 0 3 V indicating the possi bility of a hard short at the output the switching frequency is reduced to 1 4 of the internal oscillator frequency The reduction in the switching frequency gives more time for the inductor to discharge preventing a runaway of output current
44. o increase the output voltage back to regulation During the wait time between bursts both power switches are off and the output capacitor supplies all the load current Because the output voltage dips and recovers occasionally the output voltage ripple in this mode is larger than the ripple in the PWM mode of operation PULSE SKIPPING THRESHOLD The output current at which the ADP2105 ADP2106 ADP2107 transition from variable frequency PFM control to fixed frequency PWM control is called the pulse skipping threshold The pulse skipping threshold has been optimized for excellent efficiency over all load currents The variation of pulse skipping threshold with input voltage and output voltage is shown in Figure 24 Figure 26 and Figure 27 100 DUTY CYCLE OPERATION LDO MODE As the input voltage drops approaching the output voltage the ADP2105 ADP2106 ADP2107 smoothly transition to 100 duty cycle maintaining the P channel MOSFET switch on continu ously This allows the ADP2105 ADP2106 ADP2107 to regulate the output voltage until the drop in input voltage forces the P channel MOSFET switch to enter dropout as shown in the following equation Vinin Tour X Roson p D CRmp ADP2105 ADP2106 ADP2107 achieve 100 duty cycle operation by stretching the P channel MOSFET switch on time if the inductor current does not reach the peak inductor current level by the end of the clock cycle Once this happens the
45. ous conduction mode under light load conditions Finally it is important that the inductor be capable of handling the maximum peak inductor current Ir determined by the following equation AI i fg e www dzsc Ensure that the maximum rms current of the inductor is greater than the maximum load current and the saturation current of the inductor is greater than the peak current limit of the converter used in the application Table 5 Minimum Inductor Value for Common Output Voltage Options for the ADP2105 1 A Vin 22V 3 6V 4 2V 5 5V 1 2V 1 67 uH 2 00 uH 2 14 uH 2 35 uH 1 5 1 68 uH 2 19 uH 2 41 uH 2 73 uH 1 8V 2 02 uH 2 25 uH 2 57 uH 3 03 uH 25V 2 80 uH 2 80 uH 2 80 uH 3 41 uH 3 3 V 3 70 uH 3 70 uH 3 70 uH 3 70 uH Table 6 Minimum Inductor Value for Common Output Voltage Options for the ADP2106 1 5 A Vin 2 7V 3 6V 4 2V 5 5V 12 1 11 uH 2 33 uH 2 43 uH 1 56 uH 1 5V 1 25 uH 1 46 uH 1 61 uH 1 82 uH 1 8V 1 49 uH 1 50 uH 1 71 uH 2 02 uH 25V 2 08 uH 2 08 uH 2 08 uH 2 27 uH 3 3V 2 74 uH 2 74 uH 2 74 uH 2 74 uH Table 7 Minimum Inductor Value for Common Output Voltage Options for the ADP2107 2 A Vin Vout 2 7V 3 6V 4 2V 5 5V 12 0 83 uH 1 00 uH 1 07 uH 1 17 uH 1 5V 0 99 uH 1 09 uH 1 21 uH 1 36 uH 1 8V 1 19 uH 1 19 uH 1 29 uH 1 51 uH 25V 1 65 uH 1 65 uH 1 65 uH 1 70 uH 3 3V 2 18 uH 2 18 uH 2 18 uH 2 18 uH
46. sc Transition Losses Transition losses occur because the P channel MOSFET power switch cannot turn on or turn off instantaneously At the middle of an LX node transition the power switch is providing all the inductor current while the source to drain voltage of the power switch is half the input voltage resulting in power loss Transition losses increase with load current and input voltage and occur twice for each switching cycle The amount of power loss can be calculated by V Piran 9s X X ton torr X fow where ton and torr are the rise time and fall time of the LX node and are both approximately 3 ns THERMAL CONSIDERATIONS In most applications the ADP2105 ADP2106 ADP2107 do not dissipate a lot of heat due to their high efficiency However in applications with high ambient temperature low supply voltage and high duty cyde the heat dissipated in the package is large enough that it can cause the junction temperature of the die to exceed the maximum junction temperature of 125 C Once the junction temperature exceeds 140 C the converter goes into thermal shutdown It recovers only after the junction temperature has decreased below 100 C to prevent any permanent damage Therefore thermal analysis for the chosen application solution is very important to guarantee reliable performance over all conditions The junction temperature of the die is the sum of the ambient temperature of the environment and th
47. tescipin Model Current Range Output Voltage Package Description Package Option ADP2105ACPZ 1 2 R7 40 C to 125 C 16 Lead LFCSP_VQ CP 16 4 ADP2105ACPZ 1 5 R7 40 C to 125 C 16 Lead LFCSP VQ CP 16 4 ADP2105ACPZ 1 8 R7 40 C to 125 C 16 Lead LFCSP_VQ CP 16 4 ADP2105ACPZ 3 3 R7 40 C to 125 C 16 Lead LFCSP VQ CP 16 4 ADP2105ACPZ R7 40 to 125 16 Lead LFCSP_VQ CP 16 4 ADP2106ACPZ 1 2 R7 40 C to 125 16 Lead LFCSP_VQ CP 16 4 ADP2106ACPZ 1 5 R7 40 to 125 16 Lead LFCSP_VQ CP 16 4 ADP2106ACPZ 1 8 R7 40 C to 125 C 16 Lead LFCSP_VQ CP 16 4 ADP2106ACPZ 3 3 R7 40 C to 125 C 16 Lead LFCSP_VQ CP 16 4 ADP2106ACPZ R7 40 to 125 C 16 Lead LFCSP_VQ CP 16 4 ADP2107ACPZ 1 2 R7 40 C to 125 C 1 2V 16 Lead LFCSP_VQ CP 16 4 ADP2107ACPZ 1 5 R7 40 C to 125 1 5V 16 Lead LFCSP VQ CP 16 4 ADP2107ACPZ 1 8 R7 40 C to 125 C 1 8V 16 Lead LFCSP_VQ CP 16 4 ADP2107ACPZ 3 3 R7 40 C to 125 C 3 3V 16 Lead LFCSP_VQ CP 16 4 ADP2107ACPZ R7 40 to 125 ADJ 16 Lead LFCSP_VQ CP 16 4 ADP2105 1 8 EVALZ 1 8V Evaluation Board ADP2105 EVALZ Adjustable but set to 2 5 V Evaluation Board ADP2106 1 8 EVALZ 1 8V Evaluation Board ADP2106 EVALZ Adjustable but set to 2 5 V Evaluation Board ADP2107 1 8 EVALZ 1 8V Evaluation Board ADP2107 EVALZ Adjustable but set to 2 5 V Evaluation Board 17 RoHS Compliant Part Rev A Page 31 of 32 OD
48. to account for the loss of capacitance due to output voltage dc bias Figure 40 shows the loss of capacitance due to output voltage dc bias for a few X5R MLCC capacitors from Murata 20 CAPACITANCE CHANGE 14 0805 X5R MURATA GRM21BR61A475K 210 0805 X5R MURATA GRM21BR61A106K 322uF 0805 X5R MURATA GRM21BR60J226M 06079 060 VOLTAGE Vpc Figure 40 96 Drop In Capacitance vs DC Bias for Ceramic Capacitors Information Provided by Murata Corporation For example to get 20 uF output capacitance at an output voltage of 2 5 V based on Figure 40 as well as give some margin for temperature variance it is suggested that a 22 uF and a 10 uF capacitor be used in parallel to ensure that the output capacitance is sufficient under all conditions for stable behavior Table 9 Recommended Input and Output Capacitor Selection for the ADP2105 ADP2106 ADP2107 Vendor Capacitor Murata Taiyo Yuden 4 7 uF 10V GRM21BR61A475K LMK212BJ475KG X5R 0805 10 uF 10V GRM21BR61A106K LMK212BJ106KG X5R 0805 22 uF 6 3 V GRM21BR60J226M JMK212BJ226MG X5R 0805 INPUT CAPACITOR SELECTION The input capacitor reduces input voltage ripple caused by the switch currents on the PWIN pins Place the input capacitors as close as possible to the PWIN pins Select an input capacitor capable of withstanding the rms input current for the maximum load current in your application For the ADP2105 it is recommend
49. ts or other suse Specifications subject to change without notice No One Technology Way P O Box 9106 Norwood MA 02062 9106 U S A ise under any patent or patent rights of Analog Devices Tel 781 329 4700 www analog com 4 the property of their respective owners Fax 781 461 3113 2006 2007 Analog Devices Inc All rights reserved 1g E www dzsc ADP2105 ADP2106 ADP2107 TABLE OF CONTENTS 1 Puoi 1 General 1 Typical Performance Characteristics 222 1 Typical Operating Circuit sese 1 Revision History 2 SPeciNCaONS M AT 3 Absolute Maximum Ratings essent 5 Thermal 5 Boundary Coma ition 5 ipie o E 5 Pin Configuration and Function 6 Typical Performance Characteristics sse 7 Theory of Operation 13 Control Scheme oet a RI ERR 13 PWM Mode Operation esee 13 PEM Mode retineret tnt tnnt 13 Pulse Skipping Threshold sss 13 100 Duty Cycle Operation LDO 13
50. und reference of power components such as input and output capacitors to power ground In addition connect both the ground planes to the exposed pad of the ADP2105 ADP2106 ADP2107 e PWIN pin place an input capacitor as close to the PWIN pin as possible and connect the other end to the closest power ground plane e Place the 0 1 uF 10 low pass input filter between the IN pin and the PWINI pin as close to the IN pin as possible e Ensure that the high current loops are as short and as wide as possible Make the high current path from Cm through L Cour and the PGND plane back to Cw as short as possible To accomplish this ensure that the input and output capacitors share a common PGND plane Rev A Page 26 of 32 0 f www dzsc Make the high current path from the PGND pin of the ADP2105 ADP2106 ADP2107 through L and Cour back to the PGND plane as short as possible To do this ensure that the PGND pin of the ADP2105 ADP2106 ADP2107 is tied to the PGND plane as close as possible to the input and output capacitors Place the feedback resistor divider network as close as possible to the FB pin to prevent noise pickup Try to minimize the length of trace connecting the top of the feedback resistor divider to the output while keeping away from the high current traces and the switch node LX that can lead to noise pickup To reduce noise pickup place an analog ground plane on either side of the FB trace
51. via correlation using standard statistical quality control SQC Typical values are at Ta 25 C Guaranteed by design 3 The ADP2015 ADP2106 ADP2107 line regulation was measured in a servo loop on the ATE that adjusts the feedback voltage to achieve a specific comp voltage All LX switch node characteristics are guaranteed only when the LX1 and LX2 pins are tied together gt These specifications are guaranteed from 40 C to 85 Rev A Page 4 of 32 www dzsc ADP2105 ADP2106 ADP2107 ABSOLUTE MAXIMUM RATINGS Table 2 Parameter Rating IN EN SS COMP OUT_SENSE FB to 0 3V to 6 V AGND LX1 LX2 to PGND 0 3 V to Vin 0 3 V PWIN1 PWIN2 to PGND 0 3V to 6 V PGND to AGND 0 3 V to 0 3 V GND to AGND 0 3 V to 0 3 V PWIN1 PWIN2 to IN 0 3 V to 40 3 V Operating Junction Temperature Range 40 C to 125 C Storage Temperature Range 65 C to 150 Soldering Conditions JEDEC J STD 020 THERMAL RESISTANCE is specified for the worst case conditions that is a device soldered in a circuit board for surface mount packages Table 3 Thermal Resistance Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device This is a stress rating only functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied

ANALOG DEVICES ADP2105/ADP2106/ADP2107 handbook

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