NATIONAL SEMICONDUCTOR LM2700 Manual
Contents
1. dn deis YSZ zHINSZ L ZH4009 00227 LIFE SUPPORT POLICY NATIONAL S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION As used herein 1 Life support devices or systems are devices or 2 A critical component is any component of a life systems which a are intended for surgical implant support device or system whose failure to perform into the body or b support or sustain life and can be reasonably expected to cause the failure of whose failure to perform when properly used in the life support device or system or to affect its accordance with instructions for use provided in the safety or effectiveness labeling can be reasonably expected to result in a significant injury to the user BANNED SUBSTANCE COMPLIANCE National Semiconductor certifies that the products and packing materials meet the provisions of the Customer Products Stewardship Specification CSP 9 111C2 and the Banned Substances and Materials of Interest Specification CSP 9 111S2 and contain no Banned Substances as defined in CSP 9 111S2 National Semiconductor National Semiconductor National Semiconductor National Semiconductor Americas Customer Europe Customer Support Center Asia Pacific Customer Japan Customer Support Center Support Center Fax 49 0 180 530 85 86 Support Center Fax 81 3 56392. National Semiconductor LM2700 May 2004 600kHz 1 25MHz 2 5A Step up PWM DC DC Converter General Description The LM2700 is step up DC DC converter with a 3 6A 80mQ internal switch and pin selectable operating fre quency With the ability to produce 500mA at 8V from a single Lithium lon battery the LM2700 is an ideal part for biasing LCD displays The LM2700 can be operated at switching frequencies of 600kHz and 1 25MHz allowing for easy filtering and low noise An external compensation pin gives the user flexibility in setting frequency compensation which makes possible the use of small low ESR ceramic capacitors at the output The LM2700 features continuous switching at light loads and operates with a switching quies cent current of 2 0mA at 600kHz and 3 0mA at 1 25MHz The LM2700 is available in a low profile 14 lead TSSOP package or a 14 lead LLP package Features 3 6A 0 080 internal switch m Operating input voltage range of 2 2V to 12V m input undervoltage protection m Adjustable output voltage up to 17 5V 600kHz 1 25MHz pin selectable frequency operation m Over temperature protection m Small 14 Lead TSSOP or LLP package Applications LCD Bias Supplies m Handheld Devices m Portable Applications m GSM CDMA Phones m Digital Cameras Typical Application Circuit L 22V 3 3V SHDN 47 uF t D1 FSLCT LM2700 Cour 22 uF Ceramic 20012301 600 kHz Op
3. In the first cycle of operation shown in Figure 1 a the transistor is closed and the diode is reverse biased Energy is collected in the inductor and the load current is supplied by The second cycle is shown Figure 1 b During this cycle the transistor is open and the diode is forward biased The energy stored in the inductor is transferred to the load and output capacitor The ratio of these two cycles determines the output voltage The output voltage is defined approximately as where D is the duty cycle of the switch D and D will be required for design calculations SETTING THE OUTPUT VOLTAGE The output voltage is set using the feedback pin and a resistor divider connected to the output as shown in Figure 3 The feedback pin voltage is 1 26V so the ratio of the feed back resistors sets the output voltage according to the fol lowing equation Vou 1 26 2 156 R INTRODUCTION TO COMPENSATION 1 A t s D Ts Ts b 20012305 FIGURE 2 a Inductor current b Diode current www national com Operation Continued The LM2700 is a current mode PWM boost converter The signal flow of this control scheme has two feedback loops one that senses switch current and one that senses output voltage To keep a current programmed control converter stable above duty cycles of 5096 the inductor must meet certain criteria The inductor along with i
4. 7507 Email new feedback 9 nsc com Email europe support nsc com Email ap support nsc com Email jpn feedback 9 nsc com Tel 1 800 272 9959 Deutsch Tel 49 0 69 9508 6208 Tel 81 3 5639 7560 English Tel 44 0 870 24 0 2171 www national com Frangais Tel 33 0 1 41 91 8790 National does not assume any responsibility for use of any circuitry described no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications
5. Block Diagram FSLCT EJ Bandgap Voltage Reference Detailed Description The LM2700 utilizes a PWM control scheme to regulate the output voltage over all load conditions The operation can best be understood referring to the block diagram and Figure 1 of the Operation section At the start of each cycle the oscillator sets the driver logic and turns on the NMOS power device conducting current through the inductor cycle 1 of Figure 1 a During this cycle the voltage at the pin controls the peak inductor current The voltage will in crease with larger loads and decrease with smaller This voltage is compared with the summation of the SW voltage and the ramp compensation The ramp compensation is used in PWM architectures to eliminate the sub harmonic oscillations that occur during duty cycles greater than 50 Once the summation of the ramp compensation and switch voltage equals the Vc voltage the PWM comparator resets Oscillator Shutdown 85 Duty wed Load Current Cycle Limit Measurement SW Shutdown Supply Comparator GND SHDN Vin 20012303 the driver logic turning off the NMOS power device The inductor current then flows through the schottky diode to the load and output capacitor cycle 2 of Figure 1 6 The 5 power device is then set by the oscillator at the end of the period and current flows through the inductor once again The LM2700 has dedicated protection circuitry r
6. CH2 500mV div AC Coupled CH3 Inductor Current 1A div DC Coupled 20us div Load Transient for Figure 5 2 5V 4 2V 15 4H D SW ViN FSLCT LM2700 Battery or 12V Power Source Cour 33 pF Tantalum 20012333 FIGURE 6 600 kHz operation 12V output 13 www national com 00ZcIN 1 LM2700 Application Information continued 20012351 Vin 3 3 lout 50mMA 350mA gt 50mA CH1 lout 0 5A div DC Coupled CH2 500mV div AC Coupled CHS Inductor Current 1A div DC Coupled 50us div Load Transient for Figure 6 04 05 06 07 23V O Vin 2 5 4 2V SW ViN FSLCT LM2700 SHDN 47 uF c 20012308 FIGURE 7 Triple Output TFT Bias 600 kHz operation www national com 14 Application Information continued ET MOM C epu voa a Nep dex NI Vd we wg eges 2 NE qe 3 20012349 Vin 3 3V lour 500mA CH1 2V div DC Coupled CH2 5V div DC Coupled CH3 Inductor Current 500mA div DC Coupled 1ms div Start Up Waveform for Figure 7 1 m uS dod Bos dubi medo dra 2 gt n E E EE E E eM ES a we 3 METTE TIE ETE 20012350 Vin 3 3 lout 50mMA 375mA gt 50mA CH1 lour 0 2A div DC Coupled CH2 Vout 2V div AC Coupled CH3 Inductor C
7. exceed the switch current limit Using Schottky diodes with lower forward voltage drop will decrease power dissipa tion and increase efficiency DC GAIN AND OPEN LOOP GAIN Since the control stage of the converter forms a complete feedback loop with the power components it forms a closed loop system that must be stabilized to avoid positive feed back and instability A value for open loop DC gain will be required from which you can calculate or place poles and zeros to determine the crossover frequency and the phase margin A high phase margin greater than 45 is desired for the best stability and transient response For the purpose of stabilizing the LM2700 choosing a crossover point well be low where the right half plane zero is located will ensure sufficient phase margin A discussion of the right half plane zero and checking the crossover using the DC gain will follow INPUT AND OUTPUT CAPACITOR SELECTION The switching action of a boost regulator causes a triangular voltage waveform at the input A capacitor is required to reduce the input ripple and noise for proper operation of the regulator The size used is dependant on the application and board layout If the regulator will be loaded uniformly with www national com 00ZcIN 1 LM2700 Operation continued very little load changes and at lower current outputs the input capacitor size can often be reduced The size can also be reduced if the input of th
8. to the Compensation section for other design requirement COMPENSATION This section will present a general design procedure to help insure a stable and operational circuit The designs in this datasheet are optimized for particular requirements If differ ent conversions are required some of the components may need to be changed to ensure stability Below is a set of general guidelines in designing a stable circuit for continu ous conduction operation loads greater than approximately 100 in most all cases this will provide for stability during discontinuous operation as well The power components and their effects will be determined first then the compensation components will be chosen to produce stability INDUCTOR AND DIODE SELECTION Although the inductor sizes mentioned earlier are fine for most applications a more exact value can be calculated To ensure stability at duty cycles above 50 the inductor must have some minimum value determined by the minimum input voltage and the maximum output voltage This equa tion is 8 gt VinRoson D 0 144 fs B pi where fs is the switching frequency D is the duty cycle and Rpsow is the ON resistance of the internal switch taken from the graph Rpson vs in the Typical Performance Char acteristics section This equation is only good for duty cycles greater than 50 D gt 0 5 for duty cycles less than 50 the recommended values may be used The corresponding in
9. F bypass capacitor can be placed in parallel with Cin close to the V pin to shunt any high frequency noise to ground The output ca pacitor Cour should also be placed close to the IC Any copper trace connections for the Cour capacitor can in crease the series resistance which directly effects output voltage ripple The feedback network resistors Reg and should be kept close to the FB pin and away from the inductor to minimize copper trace connections that can in ject noise into the system Trace connections made to the inductor and schottky diode should be minimized to reduce power dissipation and increase overall efficiency For more detail on switching power supply layout considerations see Application Note AN 1149 Layout Guidelines for Switching Power Supplies SW LM2700 FSLCT 8V GND Cour 22 20012331 FIGURE 3 600 kHz operation 8V output www national com 00ZcIN 1 LM2700 Application Information 2 5V 4 2V Battery or 8V Power Source Cour 10 Ceramic 20012330 FIGURE 4 1 25 MHz operation 8V output 2 5V 4 2V 2 2 uH D SW Vin FSLCT LM2700 Battery or P ower SHDN Vc Source Cour 33 uF Tantalum 20012332 FIGURE 5 600 kHz operation 5V output www national com Application Information continued 20012352 Vin 3 3V lour 200 gt 700mA gt 200mA CH1 lout 0 5A div DC Coupled
10. amage to the device may occur Operating Ratings are conditions for which the device is intended to be functional but device parameter specifications may not be guaranteed For guaranteed specifications and test conditions see the Electrical Characteristics www national com Electrical Characteristics continued Note 3 The maximum allowable power dissipation is a function of the maximum junction temperature MAX the junction to ambient thermal resistance and the ambient temperature TA See the Electrical Characteristics table for the thermal resistance The maximum allowable power dissipation at any ambient temperature is calculated using Pp MAX Tmax Exceeding the maximum allowable power dissipation will cause excessive die temperature and the regulator will go into thermal shutdown Note 4 The human body model is a 100 pF capacitor discharged through a 1 5kQ resistor into each The machine model is a 200pF capacitor discharged directly into each pin Note 5 All limits guaranteed at room temperature standard typeface and at temperature extremes bold typeface All room temperature limits are 100 tested or guaranteed through statistical analysis All limits at temperature extremes are guaranteed via correlation using standard Statistical Quality Control SQC methods limits are used to calculate Average Outgoing Quality Level AOQL Note 6 Typical numbers are at 25 C and re
11. ators HIGH OUTPUT CAPACITOR ESR COMPENSATION When using an output capacitor with a high ESR value or just to improve the overall phase margin of the control loop another pole may be introduced to cancel the zero created by the ESR This is accomplished by adding another capaci tor directly from the compensation pin to ground in parallel with the series combination of Rc and Cc The pole should be placed at the same frequency as fz the ESR zero The equation for this pole follows 1 ea in Hz To ensure this equation is valid and that can be used without negatively impacting the effects of Rc and Cc must be greater than 1056 CHECKING THE DESIGN The final step is to check the design This is to ensure a bandwidth of 12 or less of the frequency of the RHP zero This is done by calculating the open loop DC gain Apc After this value is known you can calculate the crossover visually by placing a 20dB decade slope at each pole and a 20dB decade slope for each zero The point at which the gain plot crosses unity gain or OdB is the crossover frequency If the crossover frequency is less than 1 2 the RHP zero the phase margin should be high enough for stability The phase mar www national com Operation Continued gin can also be improved by adding as discussed earlier in the section The equation for Apc is given below with additional equations required for
12. by the ESR of the output capacitor is generally very high frequency if the ESR is small If low ESR capacitors are used it can be neglected If higher ESR capacitors are used see the High Output Capacitor ESR Compensation section RIGHT HALF PLANE ZERO A current mode control boost regulator has an inherent right half plane zero RHP zero This zero has the effect of a zero in the gain plot causing an imposed 20dB decade on the rolloff but has the effect of a pole in the phase subtracting another 90 in the phase plot This can cause undesirable effects if the control loop is influenced by this zero To ensure the RHP zero does not cause instability issues the control loop should be designed to have a bandwidth of less than 12 the frequency of the RHP zero This zero occurs at a fre quency of Voy D RHPzero Onl in Hz LOAD where 1 is the maximum load current SELECTING THE COMPENSATION COMPONENTS The first step in selecting the compensation components Rc and is to set a dominant low frequency pole in the control loop Simply choose values for Ro and Ce within the ranges given in the Introduction to Compensation section to set this pole in the area of 10Hz to 500Hz The frequency of the pole created is determined by the equation 1 L in Hz 2n Ro where is the output impedance of the error amplifier approximately 850kQ Since Rc is general
13. ductor current ripple as shown in Figure 2 a is given by in H Ai nAmps inductor ripple current is important for few reasons One reason is because the peak switch current will be the average inductor current input current or plus Ai As a side note discontinuous operation occurs when the inductor current falls to zero during a switching cycle or Ai is greater than the average inductor current Therefore con tinuous conduction mode occurs when Ai is less than the average inductor current Care must be taken to make sure that the switch will not reach its current limit during normal operation The inductor must also be sized accordingly It should have a saturation current rating higher than the peak inductor current expected The output voltage ripple is also affected by the total ripple current The output diode for a boost regulator must be chosen correctly depending on the output voltage and the output current The typical current waveform for the diode in con tinuous conduction mode is shown in Figure 2 b The diode must be rated for a reverse voltage equal to or greater than the output voltage used The average current rating must be greater than the maximum load current expected and the peak current rating must be greater than the peak inductor current During short circuit testing or if short circuit condi tions are possible in the application the diode current rating must
14. e regulator is very close to the Source output The size will generally need to be larger for applications where the regulator is supplying nearly the maximum rated output or if large load steps are expected A minimum value of 10 should be used for the less stressful condtions while or 47 capacitor may be required for higher power and dynamic loads Larger values and or lower ESR may be needed if the application requires very low ripple on the input source voltage The choice of output capacitors is also somewhat arbitrary and depends on the design requirements for output voltage ripple It is recommended that low ESR Equivalent Series Resistance denoted Resp capacitors be used such as ceramic polymer electrolytic or low ESR tantalum Higher ESR capacitors may be used but will require more compen sation which will be explained later on in the section The ESR is also important because it determines the peak to peak output voltage ripple according to the approximate equation AVout 24i Resp in Volts A minimum value of 10 is recommended and be increased to a larger value After choosing the output capaci tor you can determine a pole zero pair introduced into the control loop by the following equations 1 f Hz PU 2m Rese R Cour E ON D 2 2 Where R is the minimum load resistance corresponding to the maximum load current The zero created
15. emperature Switch Current Limit vs Vin 2 25 2 PON 2 2 5 5 2 2 Temperature 9C VIN 20012320 20012322 Rpsow VS Vin lo VS Vin 2A 600 kHz not switching E E lt 1 E 2 oF Vin V Vin V 20012327 20012328 lo vs Vin lo vs Vin 600 kHz switching 1 25 MHz not switching iE E 20012329 20012321 www national com 6 Typical Performance Characteristics Continued Iq mA Switching Frequency kHz 650 645 640 635 650 625 620 615 610 605 600 la VS Vin 1 25 MHz switching 20012319 Frequency vs Vin 600 kHz 20012323 VS Vin In shutdown 20012318 Frequency vs Vin 1 25 MHz Switching Frequency MHz 20012324 www national com 00ZcIN 1 LM2700 Operation L Vin E PWM L X Vin Cour Riowp Vin V OUT 20012302 Road OUT Cycle 2 b FIGURE 1 Simplified Boost Converter Diagram a First Cycle of Operation b Second Cycle Of Operation CONTINUOUS CONDUCTION MODE The LM2700 is a current mode PWM boost regulator A boost regulator steps the input voltage up to a higher output voltage In continuous conduction mode when the inductor current never reaches zero at steady state the boost regu lator operates in two cycles
16. eration 2004 National Semiconductor Corporation DS200123 www national com 49149Au02 dn deis zHINSZ L ZH4009 00227 LM2700 Connection Diagram Top View 20012304 14 Lead TSSOP or LLP Ordering Information Order Number Package Type NSC Package Drawing Supplied As LM2700MT ADJ LM2700MTX ADJ LM2700LD ADJ LM2700LDX ADJ Pin Description TSSOP 14 MTC14 94 Units Rail TSSOP 14 MTC14 2500 Units Tape and Reel LLP 14 LDA14A 1000 Units Tape and Reel LLP 14 LDA14A 4500 Units Tape and Reel Pin Name Function 1 Vc Compensation network connection Connected to the output of the voltage error amplifier 2 FB Output voltage feedback input 3 SHDN Shutdown control input active low 4 AGND Analog ground 5 PGND Power ground PGND pins must be connected together directly at the part 6 PGND Power ground PGND pins must be connected together directly at the part T PGND Power ground PGND pins must be connected together directly at the part 8 SW Power switch input Switch connected between SW pins and PGND pins 9 SW Power switch input Switch connected between SW pins and PGND pins 10 SW Power switch input Switch connected between SW pins and PGND pins 11 NC Pin not connected internally 12 Vin Analog power input 13 FSLCT Switching frequency select input Vin 1 25MHz Ground 600k z 14 NC Connect to ground www national com
17. he full Operating Tempera ture Range 40 C to 125 C Unless otherwise specified Vi 2 2V and unless otherwise specified iis Min T Max Symbol Parameter Conditions Note 5 Pm Note 5 Units lo Quiescent Current FB 2 2V Not Switching 12 mA FSLCT OV FB 2 2V Not Switchin FSLCT v Int mA 5 Ves Feedback Voltage 1 2285 1 26 V Note 7 Switch Current Limit Vin 2 7V Note 8 2 55 3 6 N ep AVin Feedback Voltage Line 2 2V Vin 12 0V 0 02 0 07 Regulation lg FB Pin Bias Current 0 5 40 nA Note 9 Vin Input Voltage Range 2 2 12 V Om Error Amp Transconductance Al 5pA 40 155 290 Error Amp Voltage Gain 135 V V Dmax Maximum Duty Cycle FSLCT Ground 78 85 Minimum Duty Cycle FSLCT Ground 15 FSLCT Vin 30 fs Switching Frequency FSLCT Ground 480 600 720 kHz FSLCT Vin 1 125 15 MH ISHDN Shutdown Pin Current Vsupw Vin 0 008 OV 0 5 p IL Switch Leakage Current Vow 18V 0 02 Switch Rpson Note 10 Vin 2 7V low 2 80 Thsupn SHDN Threshold Output High 0 9 0 6 V Output Low 06 V UVP On Threshold 1 95 200 22 V Off Threshold 1 85 195 24 V Oja Thermal Resistance TSSOP package only 150 CW Note 11 LLP package only 45 Note 1 This voltage should never exceed Note 2 Absolute maximum ratings are limits beyond which d
18. ly much less than Ro it does not have much effect on the above equation and can be neglected until a value is chosen to set the zero fzc fzc is created to cancel out the pole created by the output capacitor fp4 The output capacitor pole will shift with differ ent load currents as shown by the equation so setting the zero is not exact Determine the range of fe over the ex pected loads and then set the zero fzc to a point approxi mately in the middle The frequency of this zero is deter mined by zc CLR in 2 Now can be chosen with the selected value for Cc Check to make sure that the pole fpc is still in the 10Hz to 500Hz range change each value slightly if needed to ensure both component values are in the recommended range After checking the design at the end of this section these values can be changed a little more to optimize performance if desired This is best done in the lab on a bench checking the load step response with different values until the ringing and overshoot on the output voltage at the edge of the load steps is minimal This should produce a stable high performance circuit For improved transient response higher values of Rc should be chosen This will improve the overall bandwidth which makes the regulator respond more quickly to tran sients If more detail is required or the most optimal perfor mance is desired refer to a more in depth discussion of compensating current mode DC DC switching regul
19. nput and output voltage will determine the slope of the current through the inductor see Figure 2 a If the slope of the inductor current is too great the circuit will be unstable above duty cycles of 50 A 4 7uUH inductor is recommended for most 600 kHz appli cations while a 2 2uH inductor may be used for most 1 25 MHz applications If the duty cycle is approaching the maxi mum of 85 it may be necessary to increase the inductance by as much as 2X See Inductor and Diode Selection for more detailed inductor sizing The LM2700 provides a compensation pin Vc to customize the voltage loop feedback It is recommended that a series combination of Rc and be used for the compensation network as shown in Figure 3 For any given application there exists a unique combination of Rc and Ce that will optimize the performance of the LM2700 circuit in terms of its transient response The series combination of Cc introduces a pole zero pair according to the following equa tions 1 2 where is the output impedance of the error amplifier approximately 850 For most applications performance be optimized by choosing values within the range 5kQ x Rc lt 20kQ can be up to 200kQ if is used see High Output Capacitor ESR Compensation and 680pF lt lt 4 7nF Refer to the Applications Information section for rec ommended values for specific circuits and conditions Refer
20. present the most likely norm Note 7 Duty cycle affects current limit due to ramp generator Note 8 Current limit at 0 duty cycle See TYPICAL PERFORMANCE section for Switch Current Limit vs Viy Note 9 Bias current flows into FB pin Note 10 Does not include the bond wires Measured directly at the die Note 11 Refer to National s packaging website for more detailed thermal information and mounting techniques for the LLP and TSSOP packages 00ZcIN 1 Typical Performance Characteristics Efficiency vs Load Current Efficiency vs Load Current Vour 8V fs 600 kHz Vour 8V fs 1 25 MHz 100 100 90 90 80 E 80 o o 70 70 60 60 50 50 1 10 100 1000 lour mA 20012326 20012325 Efficiency vs Load Current Efficiency vs Load Current 5V fs 600 kHz Vout 12V fs 600 kHz 100 100 90 90 I 80 80 o 2 2 70 8 70 60 60 50 20012334 20012335 5 www national com LM2700 Typical Performance Characteristics Continued Switch Current Limit vs T
21. the calculation R 20s a RE RJR n aB FB1 FB2 x lt in rad s nD L Leff 2mc 1 m1 no unit mc 0 072fs in V s 5 where is the minimum load resistance is the mini mum input voltage gm is the error amplifier transconduc tance found in the Electrical Characteristics table and Rp son is the value chosen from the graph Rpson vs Vin in the Typical Performance Characteristics section Application Information 2 5V 4 2V 4 7 uH ViN Battery or Power SHDN Source LAYOUT CONSIDERATIONS The LM2700 uses two separate ground connections PGND for the driver and NMOS power device and AGND for the sensitive analog control circuitry The AGND and PGND pins should be tied directly together at the package The feed back and compensation networks should be connected di rectly to a dedicated analog ground plane and this ground plane must connect to the AGND pin If no analog ground plane is available then the ground connections of the feed back and compensation networks must tie directly to the AGND pin Connecting these networks to the PGND can inject noise into the system and effect performance The input bypass capacitor as shown in Figure 3 must be placed close to the IC This will reduce copper trace resistance which effects input voltage ripple of the IC For additional input voltage filtering a 100n
22. unning dur ing normal operation to protect the IC The Thermal Shut down circuitry turns off the NMOS power device when the die temperature reaches excessive levels The UVP com parator protects the NMOS power device during supply power startup and shutdown to prevent operation at voltages less than the minimum input voltage The OVP comparator is used to prevent the output voltage from rising at no loads allowing full PWM operation over all load conditions The LM2700 also features a shutdown mode decreasing the supply current to 5pA www national com 00ZcIN 1 LM2700 Absolute Maximum Ratings note 2 If Military Aerospace specified devices are required please contact the National Semiconductor Sales Office Distributors for availability and specifications Vin 12V SW Voltage 18V FB Voltage 7V Vc Voltage 0 965V lt Vo lt 1 565V SHDN Voltage Note 1 7V FSLCT Note 1 12V Maximum Junction Temperature 150 C Power Dissipation Note 3 Internally Limited Lead Temperature 300 C Vapor Phase 60 sec 215 C Electrical Characteristics Infrared 15 sec ESD Susceptibility Note 4 Human Body Model Machine Model Operating Conditions Operating Junction Temperature Range Note 5 Storage Temperature Supply Voltage SW Voltage 220 C 2kV 200V 40 C to 125 C 65 to 150 C 2 2V to 12V 17 5V Specifications in standard type face are for T 25 C and those with boldface type apply over t
23. urrent 1A div DC Coupled 500us div Load Transient for Figure 7 8V Output 15 www national com 00ZcIN 1 LM2700 Physical Dimensions inches millimeters unless otherwise noted 14X 0 25 00000 3 Int 00000 12X 0 5 RECOMMENDED LAND PATTERN 1 1 RATION WITH PKG SOLDER PADS PIN 1 INDEX AREA 1 ALL LEAD TIPS 0 8 MAX DIMENSIONS ARE IN MILLIMETERS 0 2 PIN 1 ID 2 220 1 14 0 5 0 1 14 0 25 0 05 o 19 c a9 BO Rev A LLP 14 Pin Package LDA For Ordering Refer to Ordering Information Table NS Package Number LDA14A E CN 0 2 C B A 12X 0 65 0 19 0 30 ALL LEAD TIPS 0 1 0 05 0 130 ES 14 1 78 il 14X 0 P L GAGE PLANE 12 0 650 4 0 8 RECOMMENDED LAND PATTERN A E 5 T 0 6 0 1 SEATING PLANE DETAIL A TYPICAL SEE DETAIL 274 4 14X 5 St 7 DIMENSIONS ARE IN MILLIMETERS DIMENSIONS IN FOR REFERENCE ONLY 14 Rev D TSSOP 14 Pin Package MTC For Ordering Refer to Ordering Information Table NS Package Number MTC14 www national com Notes 49149Au02
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NATIONAL SEMICONDUCTOR LM2700 Manual