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ANALOG DEVICES OP292 Manual

1. FREQUENCY Hz Figure 26 OP292 OP492 PSR vs Frequency 15 V 00310 025 003 10 026 0P292 0P492 4 8 RL 100kO s 4 6 9 2 D 44 2 tu E 9 5 lt o 3 gt 4 2 zx 5 a 9 5 RL 2kQ O 40 M E S RLZ10ko 2 RL 100kO 2 3 8 9 3 50 25 0 25 50 75 100 125 3 50 25 0 25 50 75 100 125 2 TEMPERATURE C 8 TEMPERATURE C 8 Figure 27 OP292 OP492 Vour Swing vs Temperature 5 V Figure 30 OP292 OP492 Vour Swing vs Temperature 15 V 10 600 Vs BV Vom 0V 500 3 Z 5 400 u u in 72 E OP492 5 o 1 300 o lt 2 a a a OP292 E 200 2 a E E 100 0 1 g 0 50 25 0 25 50 75 100 125 2 50 25 0 25 50 75 100 125 8 TEMPERATURE C 8 TEMPERATURE C 8 Figure 28 OP292 OP492 Input Bias Current vs Temperature 5 V Figure 31 OP292 OP492 Input Bias Current vs Temperature 15 V 40 0 50 0 48 0 46 60 Dd S 0 42 Z 0 z 0 40 E Z 038 E E 0 36 a 90 uj 0 34 A Z 0 32 u 0 30 Z 100 P 328 E 5 0 26 110 0 24 0 22 0 20 120 0 18 N 0 10 100 1k 10k 100k 3 0 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 8 FREQUENCY Hz 5 Vin V 3 Figure 29 OP292 OP492 Channel Separation Figure 32 OP292 OP492 ls Current vs Co
2. 0 25 0 25 50 75 100 125 TEMPERATURE C Figure 13 OP492 Open Loop Gain vs Temperature 5 V 25 0 25 50 75 100 125 TEMPERATURE C Figure 14 OP492 Open Loop Gain vs Temperature 15 V 00310 012 00310 013 00310 014 o M FS SUPPLY CURRENT PER AMPLIFIER mA o co Vg 5V e o SUPPLY CURRENT PER AMPLIFIER mA o o a N 50 25 0 25 50 75 100 125 TEMPERATURE C Figure 15 OP292 Supply Current per Amplifier vs Temperature SLEW RATE V us 50 25 0 25 50 75 100 125 TEMPERATURE C Figure 16 OP292 Slew Rate vs Temperature 00310 015 00310 016 0P292 0P492 N o Vs 15V Vs 5V eo o e a 50 25 0 25 50 75 100 125 TEMPERATURE C 00310 018 Figure 18 OP492 Supply Current per Amplifier vs Temperature SLEW RATE Vlus 50 25 0 25 50 75 100 125 TEMPERATURE C 00310 019 Figure 19 OP492 Slew Rate vs Temperature a a z z z lt lt 9 135 9 T HH o 9 5 as a u ur o 2 N lt lt x 45 a n 1k 10k 100k 1M 10M 2 8 FREQUENCY Hz 8 FREQUENCY Hz 8 Fi
3. 125 C 2 3 V us Gain Bandwidth Product GBP 4 MHz Phase Margin Em 75 Degrees Channel Separation cs fo 1 kHz 100 dB NOISE PERFORMANCE Voltage Noise en p p 0 1 Hz to 10 Hz 25 uV p p Voltage Noise Density en f 1kHz 15 nV 4Hz Current Noise Density in 0 7 pA VHz Input voltage range is guaranteed by CMRR tests Rev C Page 5 of 20 0P292 0P492 ABSOLUTE MAXIMUM RATINGS Table 3 Parameter Rating Supply Voltage 33V Input Voltage Range 15V to 14V Differential Input Voltage v Output Short Circuit Duration Unlimited Storage Temperature Range 65 C to 150 C Operating Temperature Range 40 C to 125 C Junction Temperature Range 65 C to 125 C Lead Temperature Range Soldering 60 sec 300 C For supply voltages less than 36 V the absolute maximum input voltage is equal to the supply voltage Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device This is a stress rating only functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied Exposure to absolute maximum rating conditions for extended periods may affect device reliability THERMAL RESISTANCE Oya is specified for the worst case conditions that is a device soldered in the circuit board for the surface mount packages Table 4 Thermal Resistance Package Type Osa Bsc Unit
4. 8 Lead SOIC 158 43 C W 14 Lead SOIC 120 36 C W ESD CAUTION ESD electrostatic discharge sensitive device Charged devices and circuit boards can discharge A without detection Although this product features patented or proprietary protection circuitry damage dy 4 may occur on devices subjected to high energy ESD Therefore proper ESD precautions should be taken to avoid performance degradation or loss of functionality Rev C Page 6 of 20 0P292 0P492 TYPICAL PERFORMANCE CHARACTERISTICS 200 160 175 140 150 120 125 100 u o E E 100 z 80 z 5 75 60 50 40 25 g 20 E 0 E 0 500 400 300 200 100 0 100 200 300 400 500 0 5 0 4 0 3 0 2 0 1 0 0 1 02 03 04 05 06 8 INPUT OFFSET VOLTAGE Vos HV INPUT OFFSET VOLTAGE Vos mV B Figure 3 OP292 Input Offset Voltage Distribution amp 5 V Figure 6 OP492 Input Offset Voltage Distribution amp 5 V 320 240 Vs 15V 280 Vom 0V TA 25 C 200 720 OP AMPS 240 160 200 B o S 160 E 120 z 2 5 120 80 80 40 40 3 0 0 0 02 04 06 08 10 12 14 16 18 20 0 02 04 06 08 10 12 14 16 18 205 INPUT OFFSET VOLTAGE Vos mV INPUT OFFSET VOLTAGE Vos mV 5 Figure 4 OP292 Input Offset Voltage Distribution 15 V Figure 7 OP492 Input Offset Voltage Distribution 15 V 160 E 460 Ve
5. IMPERIAL ASTRONICS M015 003 10 041 NOTES 1 ALL RESISTORS ARE 1 25ppm C EXCEPT R5 1 100ppm C Figure 41 Low Cost Linearized Thermistor Amplifier Rev C Page 15 of 20 0P292 0P492 SINGLE SUPPLY ULTRASONIC CLAMPING LIMITING RECEIVER AMPLIFIER Figure 42 shows an ultrasonic receiver amplifier using the nonlinear impedance of low cost diodes to effectively control the gain for wide dynamic range This circuit amplifies a 40 KHz ultrasonic signal through a pair of low cost clamping amplifiers before feeding a band pass filter to extract a clean 40 kHz signal for processing The signal is ac coupled into the false ground bias node by virtue of the capacitive piezoelectric sensing element Rather than using an amplifier to generate a supply splitting bias the false ground voltage is generated by a low cost resistive voltage divider Each amplifier stage provides ac gain while passing on the dc self bias As long as the output signal at each stage is less than the forward voltage of a diode each amplifier has unrestricted gain to amplify low level signals However as the signal strength increases the feedback diodes begin to conduct shunting the feedback current and thus reducing the gain Although distorting the waveform the diodes effectively maintain a relatively constant amplitude even with large signals that otherwise would saturate the amplifier In addition this design is considerably more stable than the fe
6. Outline Package SOIC N Narrow Body R 14 Dimensions shown in millimeters and inches ORDERING GUIDE Model Temperature Range Package Description Package Option OP292GS 40 C to 125 C 8 Lead Narrow Body SOIC N R 8 OP292GS REEL 40 C to 125 C 8 Lead Narrow Body SOIC N R 8 OP292GSZ 40 C to 125 C 8 Lead Narrow Body SOIC_N R 8 OP292GSZ REEL 40 C to 125 C 8 Lead Narrow Body SOIC N R 8 OP492GS 40 C to 125 C 14 Lead Narrow Body SOIC_N R 14 OP492GS REEL 40 C to 125 C 14 Lead Narrow Body SOIC_N R 14 OP492GSZ 40 C to 125 C 14 Lead Narrow Body SOIC_N R 14 OP492GSZ REEL 40 C to 125 C 14 Lead Narrow Body SOIC_N R 14 1 Z RoHS Compliant Part Rev C Page 17 of 20 0P292 0P492 NOTES Rev C Page 18 of 20 0P292 0P492 NOTES Rev C Page 19 of 20 0P292 0P492 NOTES 1993 2009 Analog Devices Inc All rights reserved Trademarks and ANALOG registered trademarks are the property of their respective owners D00310 0 5 09 C DEVICES www analo g com Rev C Page 20 of 20
7. 00310 036 Figure 36 Universal Direct Access Arrangement for Telephone Line Interface SINGLE SUPPLY INSTRUMENTATION AMPLIFIER A low cost single supply instrumentation amplifier can be built as shown in Figure 37 The circuit uses two op amps to form a high input impedance differential amplifier Gain can be set by selecting resistor Re which can be calculated using the transfer function equation Normally Vrer is set to 0 V Then the output voltage is a function of the gain times the differential input voltage However the output can be offset by setting Ver from 0 V to 4 V as long as the input common mode voltage of the amplifier is not exceeded lt o E a I TT mg 5 ba EE lt 2 m m 00310 037 Figure 37 Single Supply Instrumentation Amplifier In this configuration the output can swing to near 0 V however be careful because the common mode voltage range of the input cannot operate to 0 V This is because of the limitation of the circuit configuration where the first amplifier must be able to swing below ground to attain a 0 V common mode voltage which it cannot do Depending on the gain of the instrumentation amplifier the input common mode extends to within about 0 3 V of zero The worst case common mode limit for a given gain can be easily calculated DAC OUTPUT AMPLIFIER The OP292 OP492 are ideal for buffering the output of single supply DACs Figure 38 shows a typical amplifier used to buffer
8. 2 Parameter Symbol Conditions Min Typ Max Unit INPUT CHARACTERISTICS Offset Voltage OP292 Vos 1 0 2 0 mV 40 C lt TA lt 85 C 1 2 2 5 mV 40 C lt TA 125 C 1 5 3 mV OP492 Vos 14 2 5 my 40 C lt TA lt 85 C 1 7 2 8 mV 40 C lt TA 125 C 2 3 mV Input Bias Current le 375 700 nA 40 C lt TA lt 125 C 0 5 1 HA Input Offset Current los 7 50 nA 40 C lt TA lt 85 C 20 100 nA 40 C lt TA lt 125 C 0 4 1 2 UA Input Voltage Range 11 11 V Common Mode Rejection Ratio CMRR Vem 11V 78 100 dB 40 C lt Ta lt 125 C 75 95 dB Large Signal Voltage Gain Avo R 10 kQ Vo 10 V 25 120 V mV 40 C lt Ta lt 85 C 10 75 V mV 40 C lt Ta lt 125 C 5 60 V mV Offset Voltage Drift AVos AT 40 C lt Ta lt 125 C 4 10 uV C Bias Current Drift Als AT 40 C lt Ta 125 C 3 pA C OUTPUT CHARACTERISTICS Output Voltage Swing Vo RL 2 KQ to GND 11 12 2 V 40 C lt TA 125 C 10 11 V R 100 kQ to GND 13 8 14 3 V 40 C lt TA lt 125 C 13 5 14 0 mV Short Circuit Current Limit Isc Short circuit to GND 8 10 5 mA POWER SUPPLY Power Supply Rejection Ratio PSRR Vs 42 25 V to 15V 75 86 dB 40 C lt Ta lt 125 C 70 83 dB Supply Current Per Amp Isy Vo 0V 1 1 4 mA Rev C Page 4 of 20 0P292 0P492 Parameter Symbol Conditions Min Typ Max Unit DYNAMIC PERFORMANCE Slew Rate SR R 210 kO 2 5 4 V us 40 C lt TA lt
9. ANALOG Dual Quad Single Supply DEVICES Operational Amplifiers OP292 0P492 FEATURES PIN CONFIGURATIONS Single supply operation 4 5 V to 33 V OUTA 1 8 V Input common mode includes ground NA Z OP292 7 outs Output swings to ground NA 3 TOP VIEW S NB s y 4 Not to Scale INB High slew rate 3 V us 8 High gain bandwidth 4 MHz Figure 1 8 Lead Narrow Body SOIC S Suffix Low input offset voltage High open loop gain No phase inversion APPLICATIONS Disk drives Mobile phones Servo controls 8 Modems and fax machines Figure 2 14 Lead Narrow Body SOIC S Suffix 0310 002 Pagers Power supply monitors and controls Battery operated instrumentation GENERAL DESCRIPTION The OP292 OP492 are low cost general purpose dual and quad The OP292 OP492 series is unity gain stable and features an operational amplifiers designed for single supply applications outstanding combination of speed and performance for single and are ideal for 5 V systems or dual supply operation The OP292 OP492 provide a high slew rate high bandwidth with open loop gain exceeding 40 000 and offset voltage under 800 Q OP292 and 1 mV OP492 With these combinations of features and low supply current the OP292 OP492 series is an excellent choice for battery operated applications Fabricated on Analog Devices Inc CBCMOS process the OP292 OP492 series has a PNP input stage that allows the input voltage range to incl
10. AVos AT 1 HV Month Bias Current Drift Als AT 40 C lt Ta lt 85 C 6 pA C 40 C lt Ta lt 125 C 400 pA C Offset Current Drift Alos AT 40 C lt Ta lt 85 C 1 5 pA C 40 C lt Ta lt 125 C 2 pA C OUTPUT CHARACTERISTICS Output Voltage Swing High Vout R 100 kQ to GND 40 C lt Ta lt 125 C 4 0 4 3 V RL 2 KO to GND 3 8 4 1 V 40 C lt TA lt 125 C 3 7 3 9 V Low Vout RL 100 kQ to V 8 20 mV 40 C lt TA lt 125 C 12 20 mV RL 2 KO to V 280 450 mV 40 C lt Ta lt 125 C 300 550 mV Short Circuit Current Limit Isc 5 8 mA POWER SUPPLY Power Supply Rejection Ratio PSRR Vs 4 5 V to 30V Vo 2V 75 95 dB 40 C lt Ta lt 125 C 70 90 dB Supply Current Per Amp Isy Vo 2V 0 8 1 2 mA Rev C Page 3 of 20 0P292 0P492 Parameter Symbol Conditions Min Typ Max Unit DYNAMIC PERFORMANCE Slew Rate SR Rus 10 kO 3 V us 40 C lt TA lt 125 C 1 2 V us Gain Bandwidth Product GBP 4 MHz Phase Margin Qm 75 Degrees Channel Separation CS fo 1 kHz 100 dB NOISE PERFORMANCE Voltage Noise en p p 0 1 Hz to 10 Hz 25 uV p p Voltage Noise Density en f 1kHz 15 nVv VHz Current Noise Density in 0 7 pA VHz Long term offset voltage drift is guaranteed by 1 000 hours life test performed on three independent wafer lots at 125 C with LTPD of 1 3 Vs 15 V Ves 0 V Vo 2 V Ta 25 C unless otherwise noted Table
11. V It is a good design practice to bypass the supply pins with a 0 1 uF ceramic capacitor It helps improve filtering of high frequency noise For dual supply operation the negative supply V must be applied at the same time or before V If V is applied before V or in the case of a loss of the V supply while either input is connected to ground or another low impedance source excessive input current may result Potentially damaging levels of input current can destroy the amplifier If this condition can exist simply add a1 kO or larger resistor in series with the input to eliminate the problem Rev C Page 13 of 20 0P292 0P492 TYPICAL APPLICATIONS DIRECT ACCESS ARRANGEMENT FOR TELEPHONE LINE INTERFACE Figure 36 shows a 5 V single supply transmit receive telephone line interface for a modem circuit It allows full duplex transmission of modem signals on a transformer coupled 600 V line ina differential manner The transmit section gain can be set for the specific modem device output Similarly the receive amplifier gain can be appropriately selected based on the modem device input requirements The circuit operates on a single 5 V supply The standard value resistors allow the use of a SIP packaged resistor array coupled with a quad op amp in a single package this offers a compact low part count solution TX GAIN ADJUST 50ko TO TELEPHONE LINE MODEM RX GAIN ADJUST 20kO 50kQ 0 11F RECEIVE RXA
12. edback type AGC The overall circuit has a gain range from 2 to 400 where the inversion comes from the band pass filter stage Operating with a Q of 5 the filter restores a clean undistorted signal to the output The circuit also works well with 5 V supply systems 12V 68pF 600kQ RECEIVER PANASONIC EFR RTB40K2 00310 042 Figure 42 40 kHz Ultrasonic Clamping Limiting Receiver Amplifier PRECISION SINGLE SUPPLY VOLTAGE COMPARATOR The OP292 OP492 have excellent overload recovery characteristics making them suitable for precision comparator applications Figure 43 shows the saturation recovery characteristics of the OP492 The amplifier exhibits very little propagation delay The amplifier compares a signal to precisely lt 0 5 mV offset error 003 10 043 Figure 43 OP492 Has Fast Overload Recovery for Comparator Applications PROGRAMMABLE PRECISION WINDOW COMPARATOR The OP292 OP492 can be used for precise level detection such as in test equipment where a signal is measured within a range see Figure 44 A pair of 12 bit DACs sets the threshold voltage level The DACs have serial interface which minimizes interconnection requirements The DAC8512 has a control resolution of 1 mV bit Therefore for 5 V supply operation the maximum DAC output is 4 095 V However the OP292 accepts a maximum input of 4 0 V DAC8512 00310 044 Figure 44 Programmable Window Comparator with 12 Bit Threshold Le
13. gs ov Vs 5V CM 140 40 C lt T4 S 125 C is os iT lt 125 C STAS 120 S00 OT AMPS 120 600 OP AMPS 100 100 o B z 8 5 8 2 2 60 60 40 40 20 8 20 0 d 0 2 0 04 08 12 16 20 24 28 32 36 40 0 05 10 15 20 25 30 35 40 45 508 TCVos uV C TCVos uV C E Figure 5 OP292 Temperature Drift TCVos Distribution 5 V Figure 8 OP492 Temperature Drift TCVos Distribution 5 V Rev C Page 7 of 20 0P292 0P492 OPEN LOOP GAIN V mV UNITS OPEN LOOP GAIN V mV 240 Vs BV 210 Vom OV 40 C STA lt 125 C 180 600 OP AMPS 150 120 TCVos uV C Figure 9 OP292 Temperature Drift TCVos Distribution 15 V 600 500 Vo 4V 400 300 200 R 10kQ 100 50 25 0 25 50 75 100 125 TEMPERATURE C Figure 10 OP292 Open Loop Gain vs Temperature 5 V 250 200 150 100 50 50 25 0 25 50 75 100 125 TEMPERATURE C Figure 11 OP292 Open Loop Gain vs Temperature 15 V 00310 009 00310 010 00310 011 Rev C Page 8 of 20 OPEN LOOP GAIN V mV UNITS OPEN LOOP GAIN V mV 200 Vs 15V Vom OV 175 40 C S TA S 125 C 600 OP AMPS 150 125 100 Figure 12 OP492 Temperature Drift TCVos Distribution 15 V 900 N w a a o co TCVos uV C 800 700 600 50 300 200 100
14. gure 17 OP292 0P492 Open Loop Gain and Phase vs Frequency 5 V Figure 20 OP292 0P492 Open Loop Gain and Phase vs Frequency 15 V Rev C Page 9 of 20 0P292 0P492 CLOSED LOOP GAIN dB COMMON MODE REJECTION dB POWER SUPPLY REJECTION dB 50 Ta 25 C V BV d V 0V 30 20 10 0 10 1k 10k 100k 1M 10M FREQUENCY Hz Figure 21 OP292 OP492 Closed Loop Gain vs Frequency 5 V Ok 100k 1M FREQUENCY Hz Figure 22 OP292 OP492 CMR vs Frequency 5 V 120 TA 25 C 100 Vs BV 80 60 40 20 100 1k 10k 100k 1M FREQUENCY Hz Figure 23 OP292 OP492 PSR vs Frequency 5 V 00310 021 00310 022 00310 023 Rev C Page 10 of 20 CLOSED LOOP GAIN dB COMMON MODE REJECTION dB POWER SUPPLY REJECTION dB 1k 10k 100k 1M 10M FREQUENCY Hz 00310 024 Figure 24 OP292 OP492 Closed Loop Gain vs Frequency 15 V oo e eo e A e N eo FREQUENCY Hz Figure 25 OP292 OP492 CMR vs Frequency 15 V
15. istor Amplifier 15 Single Supply Ultrasonic Clamping Limiting Receiver Ainplifier iier ETUR SH RR AREIS 16 Precision Single Supply Voltage Comparator 16 Programmable Precision Window Comparator 16 Outline Dimensions eene tens 17 Ordering Guide osse ROK eot eer 17 Rev C Page 2 of 20 0P292 0P492 SPECIFICATIONS ELECTRICAL CHARACTERISTICS Vs 5 V Vou 0 V Vo 2 V TA 25 C unless otherwise noted Table 1 Parameter Symbol Conditions Min Typ Max Unit INPUT CHARACTERISTICS Offset Voltage OP292 Vos 0 1 0 8 mV 40 C lt TA lt 85 C 0 3 1 2 mv 40 C lt TA lt 125 C 0 5 2 5 mV OP492 Vos 0 1 1 mV 40 C lt TA lt 85 C 0 3 1 5 mV 40 C lt TA lt 125 C 0 5 2 5 mV Input Bias Current lg 450 700 nA 40 C lt Ta lt 85 C 0 75 2 5 HA 40 C lt TA lt 125 C 3 0 5 0 uA Input Offset Current los 7 50 nA 40 C lt Ta lt 85 C 100 700 nA 40 C lt Ta lt 125 C 0 4 1 2 uA Input Voltage Range 0 4 0 V Common Mode Rejection Ratio CMRR Van OV to 4 0 V 75 95 dB 40 C lt TA lt 85 C 70 93 dB 40 C lt Ta lt 125 C 65 90 dB Large Signal Voltage Gain Avo RL 10 KO Vo 0 1 V to 4V 25 200 V mV 40 C lt Ta lt 85 C 10 100 V mV 40 C lt Ta lt 125 C 5 50 V mV Offset Voltage Drift AVos AT 40 C lt Ta lt 125 C 2 10 uV C Long Term Vos Drift
16. mmon Mode Voltage Rev C Page 11 of 20 0P292 0P492 o i TO E Kt ft ft tt eve NEE 800dV FS 100dV DIV MKR 16 9uV Hz 8 OHz 25kHz MKR 1000Hz BW 150Hz 8 Figure 33 Voltage Noise Density Rev C Page 12 of 20 0P292 0P492 APPLICATIONS INFORMATION PHASE REVERSAL The OP492 has built in protection against phase reversal when the input voltage goes to either supply rail In fact it is safe for the input to exceed either supply rail by up to 0 6 V with no risk of phase reversal However the input should not go beyond the positive supply rail by more than 0 9 V otherwise the output will reverse phase If this condition occurs the problem can be fixed by adding a 5 kO current limiting resistor in series with the input pin With this addition the input can go to more than 5 V beyond the positive rail without phase reversal An input voltage that is as much as 5 V below the negative rail will not result in phase reversal ov A 03 11 8V p p OP492 00310 034 Figure 34 Output Phase Reverse If Input Exceeds the Positive Supply V by More Than 0 9 V OIL i Ig ka Dak AM ETT VA RAO EE alec EXPL S Baa 0 Ee BEER S TERE RAN a Figure 35 No Negative Rail Phase Reversal Even with Input Signal at 5 V Below Ground 00310 035 POWER SUPPLY CONSIDERATIONS The OP292 OP492 are designed to operate equally well at single 5 V or 15 V supplies The lowest supply voltage recommended is 4 5
17. nsiderations REVISION HISTORY 5 09 Rev B to Rev C Deleted 8 Lead PDIP and 14 Lead PDIP Universal Changes to Features Section and General Description Section 1 Changed Vs 5 V to Vs 15 Vissssessssssssssssssssssssssssssssssnsesssssssoess 4 Changes to Table 3 and Table 4 sse 6 Changes to Figure 21 Caption and Figure 24 Caption 10 Changes to Figure 29 eee tt e HERE 11 Changes to Figure LT 13 Deleted OP292 SPICE Macro model Section 14 Changes to Figure 38 14 Changes to Figure 39 and Figure 41 a l5 Deleted OP492 SPICE Macro model Section 16 Changes to Figure 44 esse se ee sek ge ee ek gek ee eke ee oe gek enn 16 Updated Outline Dimensions eee 17 Changes to Ordering Guide sse 17 10 02 Rev A to Rev B Edits to Outline Dimensions seen 18 1 02 Rev 0 to Rev A Deleted Wafer Test Limits aaia arar 4 Deleted Dice Characteristics eene 4 Edits to Ordering Guide sse 20 Typical Applications s 14 Direct Access Arrangement for Telephone Line Interface 14 Single Supply Instrumentation Amplifier 14 DAC Output Amplifier iiir 14 50 Hz 60 Hz Single Supply Notch Filter 15 Four Pole Bessel Low Pass Filter sss 15 Low Cost Linearized Therm
18. s satisfactory results The amount of rejection and the Q of the filter is solely determined by one resistor and is shown in the table with Figure 39 The bottom amplifier is used to split the supply to bias the amplifier to midlevel The circuit can be modified to reject 50 Hz by simply changing the resistors in the twin T section RI through R4 from 2 67 kQ to 3 16 kQ and by changing R5 to of 3 16 kQ For best results the common value resistors can be from a resistor array for optimum matching characteristics R2 2 67kQ FILTER Q Ra KO REJECTION dB VOLTAGE GAIN am pu 4 is 1 00 2 0 1 50 2 50 8 0 1 80 oe i 10 00 38 15 NOTES 1 FOR 50Hz APPLICATION CHANGE R12 TO R4 TO 3 16kO AND R5 TO 1 58kQ 3 16kQ 2 Figure 39 Single Supply 50 Hz 60 Hz Notch Filter 00310 039 FOUR POLE BESSEL LOW PASS FILTER The linear phase filter in Figure 40 is designed to roll off at a voice band cutoff frequency of 3 6 kHz The four poles are formed by two cascading stages of 2 pole Sallen Key filters 0P292 0P492 00310 040 Figure 40 Four Pole Bessel Low Pass Filter Using Sallen Key Topology LOW COST LINEARIZED THERMISTOR AMPLIFIER An inexpensive thermometer amplifier circuit can be implemented using low cost thermistors One such implementation is shown in Figure 41 The circuit measures temperature over the range of 0 C to 70 C to an accuracy of 0 3 C as the linearization circuit works well
19. the output of a CMOS DAC that is connected for single supply operation To do that the normally current output 12 bit CMOS DAC R 2R ladder type is connected backward to produce a voltage output This operating configuration necessitates a low voltage reference In this case a 1 235 V low power reference is used The relatively high output impedance 10 kQ is buffered by the OP292 and at the same time gained up to a much more usable level The potentiometer provides an accurate gain trim for a 4 095 V full scale allowing 1 mV increment per LSB of control resolution The DAC8043 device comes in an 8 lead PDIP package providing a cost effective compact solution to a 12 bit analog channel 5V O Vout 1mV LSB OV 4 095V FS O O O LD SRI CLK DIGITAL CONTROL 00310 038 Figure 38 12 Bit Single Supply DAC with Serial Bus Control Rev C Page 14 of 20 50 Hz 60 Hz SINGLE SUPPLY NOTCH FILTER Figure 39 shows a notch filter that achieves nearly 30 dB of 60 Hz rejection while powered by only a single 12 V supply The circuit also works well on 5 V systems The filter uses a twin T configuration whose frequency selectivity depends heavily on the relative matching of the capacitors and resistors in the twin T section Mylar is a good choice for the capacitors of the twin T and the relative matching of the capacitors and resistors determines the pass band symmetry of the filter Using 1 resistors and 5 capacitors produce
20. ude ground A BiCMOS output stage enables the output to swing to ground while sinking current The OP292 OP492 series performance is specified for single or dual supply voltage operation over the extended industrial temperature range 40 C to 125 C Rev C Information fumished by Analog Devices is believed to be accurate and reliable However no responsibility is assumed by Analog Devices for its use nor for any infringements of patents or other rights of third parties that may result fromits use Specifications subject to change without notice No One Technology Way P O Box 9106 Norwood MA 02062 9106 U S A license is granted by implication or otherwise under any patent or patent rights of Analog Devices Tel 781 329 4700 www analog com Trademarks and registered trademarks are the property of their respective owners Fax 781 461 3113 1993 2009 Analog Devices Inc All rights reserved 0P292 0P492 TABLE OF CONTENTS Features EE ED e LU Lue 1 Applications OE AE 1 Pin Configurations isetu in l 1 OP e dl EE EE r a 1 REVISION S Si ie seedy De esi E R GE ee Ee 2 Specifications Me tette ee DE se 3 Electrical Characteristics seen 3 Absolute Maximum Ratings essere 6 Thermal Resistance ete RID UTR 6 ESD Caution cet EE 6 Typical Performance Characteristics sse 7 Applications Information eene 13 Phase REVETSA er ik nete a E IER ERA desde Power Supply Co
21. vel Control Rev C Page 16 of 20 0P292 0P492 OUTLINE DIMENSIONS 5 00 0 1968 4 80 0 1890 4 00 0 1574 6 20 0 2441 3 80 0 1497 5 80 0 2284 zy 0 50 0 0196 1 75 0 0688 M 0 25 0 0099 49 0 25 0 0098 1 35 0 0532 4 0 10 0 0040 P COPLANARITY 0 51 0 0201 K la 0 10 Mee m 0 0122 0 25 0 0098 120 0500 SEATING 0 25 0 0095 9 40 0 0157 PLANE 0 17 0 0067 COMPLIANT TO JEDEC STANDARDS MS 012 A A CONTROLLING DIMENSIONS ARE IN MILLIMETERS INCH DIMENSIONS 4 IN PARENTHESES ARE ROUNDED OFF MILLIMETER EQUIVALENTS FOR S REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN 5 Figure 45 8 Lead Standard Small Outline Package SOIC_N Narrow Body R 8 Dimensions shown in millimeters and inches 8 75 0 3445 E 8 55 0 3366 K 4 00 0 1575 6 20 0 2441 3 80 0 1496 5 80 0 2283 gt le 1 27 0 0500 0 50 0 0197 s BSC x45 1 75 0 0689 0 25 0 0098 0 25 0 0098 1 35 0 0531 8 0 10 0 0039 v1 F L X lle COPLANARITY gt SEATING 0 10 0 51 0 0201 PLANE 0 25 0 0098 1 27 0 0500 0 31 0 0122 0 17 0 0067 0 40 0 0157 COMPLIANT TO JEDEC STANDARDS MS 012 AB CONTROLLING DIMENSIONS ARE IN MILLIMETERS INCH DIMENSIONS 4 IN PARENTHESES ARE ROUNDED OFF MILLIMETER EQUIVALENTS FOR S REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN 8 Figure 46 14 Lead Standard Small
22. within a narrow temperature range However it can measure higher temperatures but at a slightly reduced accuracy To achieve the aforementioned accuracy the nonlinearity of the thermistor must be corrected This is done by connecting the thermistor in parallel with the 10 kO in the feedback loop of the first stage amplifier A constant operating current of 281 HA is supplied by the resistor R1 with the 5 V reference from the REF195 such that the self heating error of the thermistor is kept below 0 1 C In many cases the thermistor is placed some distance from the signal conditioning circuit Under this condition a 0 1 uF capacitor placed across R2 will help to suppress noise pickup This linearization network creates an offset voltage that is corrected by summing a compensating current with Potentiometer P1 The temperature dependent signal is amplified by the second stage producing a transfer coefficient of 10 mV C at the output To calibrate a precision decade box can be used in place of the thermistor For 0 C trim the decade box is set to 32 650 kQ and P1 is adjusted until the output of the circuit reads 0 V To trim the circuit at the full scale temperature of 70 C the decade box is then set to 1 752 KQ and P2 is adjusted until the circuit reads 0 70 V Rr 15V 10kQ NTC O P2 2000 R3 Re 70 CTRIM 10kQ 7 87kQ 1 0uF Vout 10mV C 10kQ O CTRIM Rr ALPHATHERMISTOR 13A1002 C3 2R1 0 1

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