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ANALOG DEVICES AD8013 datasheet

1. Figure 34 Closed Loop Gain Matching vs Frequency 8 G 2 R 1500 6 Ve 45V 4 S 2 v4 I 2 s Vg 5V DELAY W A 1 0 a 2 o tc o DELAY MATCHING l Figure 35 Group Delay and Group Delay Matching vs Frequency G 42 R 150Q Disable Mode Operation Pulling the voltage on any one of the D isable pins about 1 6 V up from the negative supply will put the corresponding amplifier into a disabled powered down state In this condition the amplifier s quiescent current drops to about 0 3 mA its output becomes a high impedance and there is a high level of isolation from input to output In the case of the gain of two line driver for example the impedance at the output node will be about the same as for a 1 6 kO resistor the feedback plus gain resistors in parallel with a 12 pF capacitor and the input to output isolation will be about 66 dB at5 MHz Leaving the Disable pin disconnected floating will leave the corresponding amplifier operational in the enabled state T he input impedance of the disable pin is about 40 kQ in parallel with a few picofarads When driven to 0 V with the negative supply at 5 V about 100 pA flows into the disable pin When the disable pins are driven by complementary output CM OS logic on a single 5 V supply the disable and enable times are about 50 ns When operated on dual supplies level shifting will be re
2. 0 014 0 356 2 54 0 045 1 15 BSC 12 14 Lead SOIC R 14 0 3444 8 75 0 3367 8 55 s 8 0 2440 6 20 0 2284 5 80 o a 2 o ES amp Ss P s 0 0688 1 75 0 0532 1 35 0 0196 0 50 0 0099 0 25 0 0098 0 25 X45 0 0040 0 10 4 gt ie gt 0 0500 0 0192 0 49 SEATING a PLANE ga 0 0138 0 35 2 0 0500 1 27 0 0160 0 41 0 0098 0 25 0 0075 0 19 REV A C2084 18 10 95 PRINTED IN U S A
3. 1 6 Watts O bserve D erating C urves Small Outli Input Vol Differentia Output Voltage Maximum Lower of 12 V from Vs or Vs Minimum Higher of 12 5 V from V or Vs Output Short Circuit D uration redit A e erdum Observe Power D erating C urves Storage T emperature R ange N and R Package 65 C to 125 C Operating T emperature Range AD BOISA tates ERES 40 C to 85 C Lead T emperature Range Soldering 10 sec 300 C NOTES IStresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device This is a stress rating only and functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied Exposure to absolute maximum rating conditions for extended periods may affect device reliability Specification is for device in free air 14 Pin Plastic DIP Package 0j 75 C Watt 14 Pin SOIC Package 6 120 C Watt ORDERING GUIDE Maximum Power Dissipation T he maximum power that can be safely dissipated by the AD 8013 is limited by the associated rise in junction temperature The by the package Exceeding a junction temperature of 175 C for an extended period can result in device failure While the AD 8013 is internally short circuit protected this may not be enough to guarantee that the maximum junction temper ature is not exceeded und
4. 2 IT OFFSET VOLTAGE mV 4 60 40 20 0 20 40 60 80 JUNCTION TEMPERATURE C 100 120 140 Figure 7 Input Offset Voltage vs J unction Temperature 140 e o N o e o SHORT CIRCUIT CURRENT mA o eo 120 80 60 40 20 0 20 40 60 80 140 JUNCTION TEMPERATURE C 100 Figure 8 Short Circuit Current vs J unction Temperature AD8013 e eo o A Vg 55V 0 1 CLOSED LOOP OUTPUT RESISTANCE Q 1M 10M FREQUENCY 100M Hz Figure 9 Closed Loop Output Resistance vs Frequency OUTPUT RESISTANCE Figure 10 Output Resistance vs Frequency Disabled State 1k 10M 100M FREQUENCY Hz 100 10 INVERT VOLTAGE NOISE nV VHz NONINVERTING ING I VNoisE 100 1k 10k FREQUENCY Hz 100k 1M 1G 1k 100 10 CURRENT NOISE pA V Hz Figure 11 Input Current and Voltage Noise vs Frequency COMMON MODE REJECTION dB 100k 1M 10M 100M FREQUENCY Hz 1G Figure 12 Common Mode Rejection vs
5. 52 56 dB Input Offset Voltage t5V 52 56 dB Input Current 15V 5V 0 2 0 4 pA Input Current 15V 5V 5 7 pA OUTPUT CHARACTERISTICS Output Voltage Swing R 1kQ Voi Vee 0 8 1 0 V Vcc Von 0 8 1 0 V R 21509 VoL Vee 1 1 1 3 V Vcc Vou 11 1 3 V Output Current 15V 30 mA t5V 25 30 mA Short C ircuit C urrent t5V 95 mA Capacitive L oad Drive t5V 1000 pF MATCHING CHARACTERISTICS D ynamic Crosstalk G 4 2 f 5MHz 15 V 5 V 70 dB Gain Flatness M atch f 20MH 5 V 0 1 dB DC Input Offset Voltage 5V 5V 0 3 mV Input Bias Current 15V 5 V 1 0 uA REV A Model AD8013A Conditions Vs Min Typ Max Units POWER SUPPLY Operating Range Single Supply 14 2 113 V D ual Supply t2 1 6 5 V Quiescent C urrent Amplifier 15V 3 0 3 5 mA t5V 3 4 4 0 mA 6 5 V 3 5 mA Quiescent C urrent Amplifier Power Down 15V 0 25 0 35 mA t5V 0 3 0 4 mA Power Supply Rejection Ratio Input Offset V oltage Vs 2 5V to t5V 70 76 dB Input Current 5V 5V 0 03 0 2 pA Input Current 15V 5V 0 07 1 0 uA NV DISABLE CHARACTERISTICS Off Isolation f 6MHz 15V t5V 70 dB Off Output Impedance G 1 5V 5V 12 pF Turn On Time 50 ns T urn Off Time 30 ns Switching T hreshold Vs xV 1 3 1 6 1 9 V NOTES T he test circuit for differential gain and phase measurements on a 5 V supply is ac coupled Specifications subject to change without notice ABSOLUTE MAXIMUM RATINGS Supply Voltage Internal Power D issipation Plastic N
6. CLOSED LOOP GAIN NORMALIZED dB L 10M 100M FREQUENCY Hz Figure 27 Closed Loop Gain and Phase vs Frequency G 10 R 21500 General T he AD 8013 is a wide bandwidth triple video amplifier that offers a high level of performance on less than 4 0 mA per amplifier of quiescent supply current T he AD 8013 uses a proprietary enhancement of a conventional current feedback architecture and achieves bandwidth in excess of 200 M H z with low differential gain and phase errors making it an extremely efficient video amplifier input bias current enable it to be used with large values of feedback resistor with very low closed loop gain errors It is designed to offer outstanding functionality and performance at closed loop inverting or noninverting gains of one or greater Choice of Feedback amp Gain Resistors Because it is a current feedback amplifier the closed loop band width of the AD 8013 may be customized using different values of the feedback resistor T able shows typical bandwidths at different supply voltages for some useful closed loop gains when driving a load of 150 9 T he choice of feedback resistor is not critical unless it is important to maintain the widest flattest frequency response T he resistors recommended in the table are those chip resistors that will result in the widest 0 1 dB bandwidth without peaking In applications requiring the best control of
7. bandwidth 196 resistors are adequate Package parasitics vary between the 14 pin plastic DIP and the 14 pin plastic SOIC and may result in a slight difference in the value of the feedback resistor used to achieve the optimum dynamic performance Resistor values and widest bandwidth figures are shown in parenthesis for the SOIC where they differ from those of the DIP Wider bandwidths than those in the table can be attained by reducing the magnitude of the feedback resistor at the expense of increased peaking while peaking can be reduced by increasing the magnitude of the feedback resistor Increasing the feedback resistor is especially useful when driving large capacitive loads as it will increase the phase margin of the closed loop circuit Refer to the section on driving capacitive loads for more information REV A T o estimate the 3 dB bandwidth for closed loop gains of 2 or greater for feedback resistors not listed in the following table the following single pole model for the AD 8013 may be used G ACL IFSC R Gn rin C1 transcapacitance 1 pF Rp feedback resistor G ideal closed loop gain ju Gn R G rin inverting input resistance 150 Q ACL closed loop gain The 3 dB bandwidth is determined from this model as 1 2n C Re Gn rin T his model will predict 3 dB bandwidth to within about 1096 to 15 of the correct value when the load is 150 O and Vs 5 V For lower supply voltages there w
8. ANALOG DEVICES Single Supply Low Power Triple Video Amplifier AD8013 FEATURES Three Video Amplifiers in One Package Drives Large Capacitive Load Excellent Video Specifications R 150 Q Gain Flatness 0 1 dB to 60 MHz 0 02 Differential Gain Error 0 06 Differential Phase Error Low Power Operates on Single 5 V to 13 V Power Supplies 4 mA Amplifier Max Power Supply Current High Speed 140 MHz Unity Gain Bandwidth 3 dB Fast Settling Time of 18 ns 0 1 1000 V s Slew Rate High Speed Disable Function per Channel Tum Off Time 30 ns Easy to Use 95 mA Short Circuit Current Output Swing to Within 1 V of Rails APPLICATIONS LCD Displays Video Line Driver Broadcast n a Compu Consum RGB Amplifier in Component Systems PRODUCT DESCRIPTION T he AD 8013 is a low power single supply triple video amplifier Each of the three amplifiers has 30 mA of output current and is optimized for driving one back terminated video load 150 Q each Each amplifier is a current feedback amp lifier and features gain flatness of 0 1 dB to 60 M H z while offering NORMALIZED GAIN dB 5 i 0 3 V 0 4 0 5 1M 10M 100M 1G FREQUENCY Hz Fine Scale Gain Flatness vs Frequency G 42 R 21500 REV A Information furnished by Analog Devices is believed to be accurate and reliable However no responsibility is assumed by Analog Devices for its use nor for
9. Frequency PSR PSR POWER SUPPLY REJECTION dB 1M 10M 100M FREQUENCY Hz 1G Figure 13 Power Supply Rejection Ratio vs Frequency eo eo TRANSIMPEDANCE dB 60 10k 100k 1M 10M 100M 1G FREQUENCY Hz PHASE Degrees li eo o Figure 14 Open Loop Transimpedance vs Frequency Relative to 1 Q REV A 30 d G 2 R Dm 40 gi Q 0 Jor pi P PHASE b 3 amp so S Vs 5V 1 99 v e RES Lu 2 60 Ves 9V 180 F o 7 i 70 0 270 9 o UN zg GAIN E n a 2 R 1509 en a 9 op Ou gt Vs 25V z ON a5 YA 100 Sd 933 E 2nd RL 1k 2 t Vg 5V 110 H Ry 1k2 aza 120 3rd 5 RL 21500 1k 10k 100k 1M 10M 100M x 1M 10M 100M 1G FREQUENCY Hz FREQUENCY Hz Figure 15 Harmonic Distortion vs Frequency Figure 18 Closed Loop Gain and Phase vs Frequency G 1 R 21500 G 10 SLEW RATE V us 1 5 2 5 3 5 4 5 5 5 6 5 7 5 OUTPUT STEP SIZE V p p SUPPLY VOLTAGE Volts Figure 16 Slew Rate vs Output Step Size Figure 19 Maximum Slew Rate vs Supply Voltag
10. NING SI the AD 8013 features proprietary ESD prote P N permanent e may occur on devices A subjected to hi atig disc jarg ef ropefESD preca Le mended to avoi atio id ity C penes om sNSITIVE DEVICE 12 6 2 o 75 210 I a NO LOAD ul gt g I lt 4 gs 6 7 R 1500 lt a wW ari 3 g 6 ul 3 E zi O 2 o o 0 0 1 2 3 4 5 6 7 1 2 3 4 5 6 7 SUPPLY VOLTAGE Volts SUPPLY VOLTAGE Volts Figure 1 Input Common Mode Voltage Range vs Figure 2 Output Voltage Swing vs Supply Voltage Supply Voltage Jas REV A Vg 55V eo o E Vg 5V OUTPUT VOLTAGE SWING V p p N 100 1k LOAD RESISTANCE Q 10k Figure 3 Output Voltage Swing vs Load Resistance 12 11 10 Vg 45V SUPPLY CURRENT mA 6 60 40 20 0 20 40 60 80 100 120 140 JUNCTION TEMPERATURE C Figure 4 Total Supply Current vs J unction Temperature 11 o SUPPLY CURRENT mA o eo 1 2 3 4 5 6 7 SUPPLY VOLTAGE Volts Figure 5 Supply Current vs Supply Voltage REV A 1 INPUT BIAS CURRENT pA o 2 lp 20 0 20 40 60 80 120 140 JUNCTION TEMPERATURE C 100 Figure 6 Input Bias Current vs J unction Temperature 1
11. and 3 to achieve the OFF channel isolation shown in Figure 40 T his circuit can achieve differential gain and phase of 0 0396 and 0 07 respectively Figure 39 2 1 Mux with High Isolation and Low Differential Gain and Phase Errors 2 1 GAIN 0 m h 1 z 4 2 o 3 m l 4 i Ww I 8 5 750 5 A o FEEDTHROUGH o 6 e0 amp 5 7 70 m uL 8 80 1M 10M 100M 1G FREQUENCY Hz Figure 40 2 1 Mux ON Channel Gain and Mux OFF Channel Feedthrough vs Frequency Gain Switching The AD 8013 can be used to build a circuit for switching between any two arbitrary gains while maintaining a constant input impedance T he example of F igure 41 shows a circuit for switching between a noninverting gain of 1 and an inverting gain of 1 T he total time for channel switching and output voltage settling is about 80 ns 6980 6980 500mV 500mV Figure 42 Switching Characteristic for Circuit of Figure 41 OUTLINE DIMENSIONS Dimensions shown in inches and mm 14 Lead Plastic DIP N 14 0 795 20 19 0 725 1 842 A 0 280 7 11 0 240 6 10 VIV Us 0 325 8 25 i 0 060 1 52 0 300 7 62 0 195 4 95 PIN 1 0 015 0 38 e 0 115 2 93 0 210 5 33 t MAX y H HHH H H 0 130 0 160 4 06 ji ING 3 30 OA15 293 e m eS MN 0 015 0 381 0 022 0 558 0 100 0 070 1 77 SEANG 0 008 0 204
12. any infringements of patents or other rights of third parties which may result from its use No license is granted by implication or otherwise under any patent or patent rights of Analog Devices PIN CONFIGURATION 14 Pin DIP amp SOIC Package DISABLE 1 1 OUT2 DISABLE 2 2 IN2 DISABLE 3 N 2 Vs 4 AD8013 Vs N 1 5 IN3 IN 1 9 N3 OUT 1 8 ours differential gain and phase error of 0 0296 and 0 06 T his makes the AD 8013 ideal for broadcast and professional video electronics T he AD 8013 offers low power of 4 mA per amplifier max and runs on a single 5 V to 13 V power supply T he outputs of each amplifier swing to within one volt of either supply rail to easily accommodate video signals The AD 8013 is unique mong its large capacitive load large capacitive ads For instance it 0 196 settling while driving 200 pF T he outstanding bandwidth of 140 M Hz along with 1000 V us of slew rate make the AD 8013 useful in many general purpose high speed applications where a single 45 V or dual power supplies up to 46 5 V are required Furthermore the AD 8013 s high speed disable function can be used to power down the amplifier or to put the output in a high impedance state T his can then be used in video multiplexing applications T he AD8013 is available in the industrial temperature range of 40 C to 85 C Channel Switching Characteristics for a 3 1 Mux Analog Devices Inc 1995 One Technolog
13. e Figure 17 Large Signal Pulse Response Gain 41 Figure 20 Small Signal Pulse Response Gain 1 Re 22 Q R 21509 Vs 5 V Re 2 kQ R 150Q Vs 5 V REV A J Pe bbb pe Siy _ P tft TAT A eel eem BLLZEHSESHE Figure 21 Large Signal Pulse Response Gain 410 Figure 24 Large Signal Pulse Response Gain 1 Re 230190 R 150 Q Vs 5 V Re 698 Q R 21500 Vs 5 V 10 R 150214 0 zm E a e o m eo PHASE PHASE e e Vg 5V T7 o a 1 N X o o 3 1 o o o AIN L eo PHASE SHIFT Degrees o PHASE SHIFT Degrees CLOSED LOOP GAIN NORMALIZED dB b m GAIN NORMALIZED dB amp bk b oa lt It a I I b Vg 5V I N om 10M 100M 1G om 10M 100M 1G FREQUENCY Hz FREQUENCY Hz Figure 22 Closed Loop Gain and Phase vs Frequency Figure 25 Closed Loop Gain and Phase vs Frequency G 10 R 21509 G 1 R 150Q N ee Slad ELCHE Seo rate vee RNC DEI waja pee ed fie Ee A jeans aE hel Figure 23 Small Signal Pulse Response Gain 10 Figure 26 Small Signal Pulse Response Gain 1 Re 23010 R 2150 Q Vs 5 V R 2698 9 R 2150 Q Vs 5 V 8 REV A AD8013 180 PHASE Vg 45V yA e PHASE SHIFT Degrees AIN Vg 5V Vg 5V
14. ee important overload conditions are input common mode voltage overdrive output voltage overdrive and input current overdrive When configured for a low closed loop gain the amplifier will quickly recover from an input common mode voltage overdrive typically in under 25 ns When con figured for a higher gain and overloaded at the output the recovery time will also be short For example in a gain of 410 with 1596 overdrive the recovery time of the AD 8013 is about 20 ns see Figure 30 For higher overdrive the response is somewhat slower For 6 dB overdrive in a gain of 410 the recovery time is about 65 ns SE A PLT tay fT PT Ee ee Figure 30 15 Overload Recovery G 10 Re 300 9 R 1 kQ Vs 5 V Figure 31 A Video Line Driver Operating at a Gain of 42 Rr Rg from Table I Gz42 3 RL21500 0 amp PHASE Ei Vs 5V 90 i Vg 5V u 1 180 T o 270 9 Za GAI E o a 1 1 4 gu ao q 96 s t ge 5 6 10M 100M FREQUENCY Hz Figure 32 Closed Loop Gain amp Phase vs Frequency for the Line Driver NORMALIZED GAIN dB I 10M 100M FREQUENCY Hz Figure 33 Fine Scale Gain Flatness vs Frequency G 2 R 150 Q 10 REV A AD8013 GAIN MATCHING dB 1M 10M 100M 1G FREQUENCY Hz
15. er all conditions T o ensure proper operation it is important to observe the derating curves It must also be noted that in noninverting gain configurations with low values of gain resistor a high level of input overdrive can result in a large input error current which may result in a significant power dissipation in the input stage T his power must be included when computing the junction temperature rise due to total internal power 2 5 M o DIP PACKAGE MAXIMUM POWER DISSIPATION Watts a Temperature Package Package Model Range Description Options AD 8013AN 40 C to 85 C 14 Pin Plastic DIP N 14 YA AD8013AR 14 40 C to 85 C 14 Pin Plastic SOIC R 14 i AD8013AR 14 REEL 40 C to 85 C 14 Pin Plastic SOIC R 14 AD 8013AR 14 REEL7 40 C to 85 C 14 Pin Plastic SOIC R 14 AD 8013ACHIPS 40 C to 85 C Die Form 350 40 30 20 10 0 10 20 30 40 50 60 70 80 90 AMBIENT TEMPERATURE C Maximum Power Dissipation vs Ambient Temperature REV A 3 AD8013 METALIZATION PHOTO Contact factory for latest dimensions Dimensions shown in inches and mm IN1 Vs DISABLE 3 3 2 DISABLE2 1 DISABLE 1 14 OUT2 0 071 1 81 CAUTION ESD electrostatic discharge sensitive device Electrostatic charges as high as 4000 V readily accumulate on the human body and test equipment and can discharge without detection Although WAR
16. ill be a slight decrease in bandwidth T he model is not accurate enough to predict either the phase behavior or the frequency response peaking of the AD 8013 It should be noted that the bandwidth is affected by attenuation due to the finite input resistance Also the open loop output resistance of about 12 Q reduces the bandwidth somewhat when driving load resistors less than about 250 9 Bandwidths will where noise gain fz e about 10 greater for load resistan ea few hundred ohms able h in and Feedback Resistor RL 1500 S C Vs Volts Gain Rp Ohms BW MHz 5 1 2000 230 2 845 931 150 135 10 301 80 1 698 825 140 130 10 499 85 5 1 2000 180 2 887 931 120 130 10 301 75 1 698 825 130 120 10 499 80 Driving Capacitive Loads When used in combination with the appropriate feedback resistor the AD 8013 will drive any load capacitance without oscillation T he general rule for current feedback amplifiers is that the higher the load capacitance the higher the feedback resistor required for stable operation D ue to the high open loop transresistance and low inverting input current of the AD 8013 the use of a large feedback resistor does not result in large closed loop gain errors Additionally its high output short circuit current makes possible rapid voltage slewing on large load capacitors For the best combination of wide bandwidth and clean pulse res
17. ponse a small output series resistor is also recommended Table II contains values of feedback and series resistors which result in the best pulse responses Figure 29 shows the AD 8013 driving a 300 pF capacitor through a large voltage step with virtually no overshoot In this case the large and small signal pulse responses are quite similar in appearance 9 AD8013 Figure 28 Circuit for Driving a Capacitive Load Tablell Recommended Feedback and Series Resistors vs Capacitive Load and Gain As noted in the warning under M aximum Power Dissipation a high level of input overdrive in a high noninverting gain circuit can result in a large current flow in the input stage T hough this current is internally limited to about 30 mA its effect on the total power dissipation may be significant High Performance Video Line Driver At a gain of 42 the AD8013 makes an excellent driver for a back terminated 75 Q video line Figures 31 32 and 33 Low differential gain and phase errors and wide 0 1 dB bandwidth can be realized T helow gain and group delay matching errors ensure excellent performance in RGB systems Figures 34 and 35 show the worst case matching Rs Ohms C pF Re Ohms G 2 G gt 3 20 2k 25 15 50 2k 25 15 100 3k 20 15 200 4k 15 15 300 6k 15 15 gt 500 7k 15 15 Figure 29 Pulse Response Driving a Large Load Capacitor C 300 pF G Rp 26k Rs 2159 Overload Recovery T he thr
18. quired from standard logic outputs to the Disable pins Figure 36 shows one possible method which results in a negligible increase in switching time REV A Vi 45V TO DISABLE PIN 4k 10k 5V V HIGH gt AMPLIFIER ENABLED V LOW gt AMPLIFIER DISABLED Figure 36 Level Shifting to Drive Disable Pins on Dual Supplies T he AD 8013 s input stages include protection from the large differential input voltages that may be applied when disabled Internal clamps limit this voltage to about 3 V T he high input to output isolation will be maintained for voltages below this limit 3 1 Video Multiplexer Wiring the amplifier outputs together will form a 3 1 mux with excellent switching behavior Figure 37 shows a recommended configuration which results in 0 1 dB bandwidth of 35 MHz and OFF channel isolation of 60 dB at 10 MHz on 5 V supplies The time to switch between channels is about 50 ns Switching time is virtually unaffected by signal level 6650 8450 Vin3 O DISABLE 3 O Figure 37 A Fast Switching 3 1 Video Mux Supply Bypassing Not Shown ILIDAI i UR TAI MVIVVVI LT ee ee Figure 38 Channel Switching Characteristic for the 3 1 Mux 11 AD8013 2 1 Video Multiplexer Configuring two amplifiers as unity gain followers and using the third to set the gain results in a high performance 2 1 mux Figures 39 and 40 T his circuit takes advantage of the very low crosstalk between C hannels 2
19. y Way P O Box 9106 Norwood MA 02062 9106 U S A Tel 617 329 4700 Fax 617 326 8703 AD8013 SPECI FICATI ONS Ta 25 C Rio 150 unless otherwise noted Model AD8013A Conditions Vs Min Typ Max Units DYNAMIC PERFORMANCE Bandwidth 3 dB No Peaking G 2 5 V 100 125 MHz No Peaking G 2 5 V 110 140 MHz Bandwidth 0 1 dB No Peaking G 2 15 V 50 MHz No Peaking G 2 5 V 60 MHz Slew Rate 2 V Step 5 V 400 V us 6 V Step 5V 600 1000 V s Settling T ime to 0 1 0V to 2 V 5V 18 ns 4 5 V Step Cig4p 200 pF 6V 40 ns Rioap gt 1 kQ Rfg 4 kQ NOISE HARMONIC PERFORMANCE Total Harmonic Distortion fe 5MHz R 1k 5V 76 dBc fc 5 MHz R 21509 5V 66 dBc Input Voltage N oise f 10kHz 15 V 5 V 3 5 nV NHz Input Current N oise f 10 kHz l y 15V 5V 12 pA NHz Differential Gain R 150 Q f23 58MHz G 42 5 V 0 05 Yo t5V 0 02 0 05 Yo Differential Phase R 150 Q f 3 58MHz G 2 5 V 0 06 D egrees 5V 0 06 0 12 D egrees DC PERFORMANCE Input Offset Voltage T min tO T max 5V 5V 2 5 mV Offset D rift 7 WC Input Bias Current 15V 5V 2 10 uA Input Bias Current T min tO T max 15V 5V 3 15 uA Open Loop T ransresistance 5 V 650 800 kQ Tmin to T max 550 kQ 5V 800k 711 Q 50 kQ INPUT CHAR Input Resistance t5 0 kQ 5 V 150 Q Input Capacitance 5 V 2 pF Input Common M ode Voltage Range 5 V 3 8 V 5 V 1 2 3 8 V Common M ode Rejection Ratio Input Offset Voltage T5 V

ANALOG DEVICES AD8013 datasheet

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